Форум » Дискуссии » Operazionnie ysiliteli ,ZAP/AZP & (продолжение) » Ответить
Operazionnie ysiliteli ,ZAP/AZP & (продолжение)
milstar: 1941: First (vacuum tube) op-amp An op-amp, defined as a general-purpose, DC-coupled, high gain, inverting feedback amplifier, is first found in US Patent 2,401,779 "Summing Amplifier" filed by Karl D. Swartzel Jr. of Bell labs in 1941. This design used three vacuum tubes to achieve a gain of 90dB and operated on voltage rails of ±350V. ###################################################### It had a single inverting input rather than differential inverting and non-inverting inputs, as are common in today's op-amps. Throughout World War II, Swartzel's design proved its value by being liberally used in the M9 artillery director designed at Bell Labs. ######################################################################### This artillery director worked with the SCR584 radar system to achieve extraordinary hit rates (near 90%) that ####################################################################### would not have been possible otherwise.[3] ########################### http://en.wikipedia.org/wiki/Operational_amplifier
milstar: https://www.eenewsanalog.com/design-center/new-phased-array-radar-architectures/page/0/3
milstar: ampling signals above the firs t Nyquist zone has become popul ar in communications, because the process is equivalent to analog demodulation. It is becoming common practice to sample IF signals directly and then use digital tec hniques to process the signal, thereby eliminating the need for an IF demodulator and filters. Clearly, howev er, as the IF frequencies become higher, the dynamic performance requirements on the ADC become more critical. The ADC input bandwidth and distortion performan ce must be adequate at the IF frequency, rather than only baseband. https://www.analog.com/media/en/training-seminars/tutorials/MT-002.pdf
milstar: The diagram above depicts how processing gain increases the performance of the ADC in the ICOM 7300. The LTC2208-14 ADC in this radio has an effective number of bits ENOB = 12.5. By itself, it can only produce dynamic range of 77 dB. However, as the sampling bandwidth is reduced from 120 million samples per second down to a 12 kHz low if, the DSP introduces another 39 dB of dynamic range. This SDR receiver processing gain is equivalent to bolting another 6.5 bits onto the ADC. http://play.fallows.ca/wp/radio/software-defined-radio/sdr-receiver-processing-gain-create-virtual-bits/
milstar: https://www.teledyne-e2v.com/content/uploads/2018/12/0869B_Dither_AN.pdf
milstar: https://apps.dtic.mil/dtic/tr/fulltext/u2/a196569.pdf he maximum scanning speed is proportional to the square of the detection bandwidth.
milstar: Oversampling R atio up to 256 from the drop -down menu located in the Configure tab , as shown in Figure 4. The low frequency 1/f noise of the system, which starts to dominate at lower output data rates less than 20 kSPS , limits the ach ievable maximum dynamic range . https://www.analog.com/media/en/technical-documentation/application-notes/AN-1279.pdf
milstar: Typically, it cannot be assumed that the SFDR across a narrow frequency band can be extrapolated to get the same performance across a wider or full Nyquist band of Fs/2. This is primarily because the frequency planning for the narrowband of the fundamental is intentionally established to filter and push higher harmonics out of the frequency band of interest. If the filter was removed, then these harmonics and other spurs would now be part of the wideband SFDR seen in the system (Figures 2 and 3). https://www.electronicdesign.com/analog/understanding-spurious-free-dynamic-range-wideband-gsps-adcs
milstar: While there are many high-performance component choices for this part of the system, even the best solutions will embed some small differential imbalances that distort the signal of interest and decrease the SFDR through the ADC. Phase mismatch between each side of the differential input signal at the front end of the ADC creates an increase in power for the harmonics of the fundamental signal. This can happen when one side of the differential signal leads the other side in time by some amount of phase relative to its period. The effect can be seen in Figure 4, when one side of a differential pair leads the other side by a small margin of periodic phase.
milstar: https://www.analog.com/media/en/training-seminars/tutorials/MT-003.pdf
milstar: https://www.analog.com/en/technical-articles/28-nm-adcs-enable-next-gen-electronic-warfare-rec-sys.html Next-Generation Electronic Warfare Receiver Systems
milstar: AD9208 14 bit 2*1.5 GSPS 0.022 mkm CMOS https://www.analog.com/media/en/technical-documentation/data-sheets/AD9208.pdf SFDR Fin 2600 mhz 78 db Fin 1800 mhz 81 db Fin 900 mhz 78 db ENOB 9.6 -9,7 SINAD 59.7-9
milstar: https://www.analog.com/en/technical-articles/Use-Noise-Spectral-Density-to-Evaluate-ADCs-in-Software-Defined-Systems.html
milstar: For example, GSM specs call for receivers that can accurately digitize signals from -13 dBm to -104 dBm in the presence of many other signals (Figure 1)—a 91-dB dynamic range! This implies that the spurious-free dynamic range (SFDR) of the converter and analog front end must be about 95 to 100 dBFS. SFDR for a converted signal with a given amplitude is the log ratio (dB) of that amplitude to the largest spurious frequency component found in the converter's Nyquist spectrum (0 to Fs/2 Hz). https://www.analog.com/en/analog-dialogue/articles/wideband-radios-need-wide-dynamic-range-converters.html
milstar: Head room: When A/D converters receive multiple channels in a broadband architecture, each signal level must be considerably less than full scale of the converter.One signal alone may use the full-scale range of the converter, but when two signals may be present, each must be half-amplitude (-6 dB), assuming equal signal power, to prevent output clipping as these signals sum together at their peaks. Each doubling of the number of signals requires individual levels to be reduced by 6 dB. For example, -12 dBFS for 4 channels, -18 dBFS for 8 channels. A multi-channel radio must have enough dynamic range to account for the SNR lost through reduced usable signal levels. In addition, radio designers keep from 3 to 15 dB in reserve as headroom at the top of the ADC range to prevent clipping that comes from inevitable high incoming peak-to-rms ratios and saturation as additional signals come in band as new callers enter the cell zone.
milstar: Converters for such radios require a sample rate at least twice the highest frequency (Nyquist rate), i.e., 20 MSPS minimum for signal range from dc to 10 MHz, and generally with at least 20% additional margin, raising the required encode rate to about 25 MSPS.
milstar: https://www.winradio.com/home/g35ddci-s.htm Receiver type Direct-sampling, digitally down-converting software-defined receiver Frequency range 1 kHz to 45 MHz SFDR 111 dB min. (preamp off) 108 dB min. (preamp on) MDS -128 dBm @ 10 MHz, 500 Hz BW (preamp off) -135 dBm @ 10 MHz, 500 Hz BW (preamp on) ADC 16 bit, 100 MSPS https://www.winradio.com/home/g35ddci.htm This is the first time a receiver of such advanced specification and unique combination of features is being offered to the general marketplace. The receiver is intended for government, military, security, surveillance, broadcast monitoring, industrial and demanding consumer applications.
milstar: https://www.winradio.com/home/g39ddce-s.htm
milstar: http://www.ti.com/lit/ug/tidubs6/tidubs6.pdf radar RF sampling with 2*14 bit ADC 2*1.5 GSPS
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/238718fa.pdf 8.192V P-P Differential Inputs http://www.ti.com/lit/an/slyt090/slyt090.pdf 8.192 v p-p = +22dbm http://wa8lmf.net/miscinfo/dBm-to-Microvolts.pdf input signal level 7 dB below full-scale input (–7 dBFS) seems to give good results and is commonly used.
milstar: SFDR = 2/3 (IIP3 - Noise Floor) SFDR = 2/3 (IIP3 - Noise Floor) - SNR(min) Both are correct , the second one is more general form as if the minimum SNR=0dB (i.e. the noise equal to the signal) then u get the first form but if u need to have the minimum detectable signal larger than the noise by a certain factor (SNR_min) then use the second regards, SFDR = [(2/3)(IIP3 – MDS)] where Noise Floor = -174dBm/Hz + 10log(B) + NF where NF -Noise Figure
milstar: AD9467 16 bit 250 msps SiGe 0.18 micron EV12AD550 12 bit 1.6 gsps BiCMOS 0.13 micron AD9213 12 bit 10.25 GSPS CMOS 0.022 micron 3600 $
milstar: https://www.analog.com/media/cn/training-seminars/design-handbooks/3689418379346Section5.pdf
milstar: http://www.ti.com/lit/an/slaa594a/slaa594a.pdf We will use the example of a 70-MHz signal with 20-MHz bandwidth (60 MHz to 80 MHz) for the discussion throughout this paper. For a radar application and for communication systems, generally 70 MHz is used as IF (intermediate frequency) with a specific bandwidth ranging from a few KHz to a few MHz. The maximum frequency component is 80 MHz in this signal. For an oversampling case, the minimum sampling rate is more than 160 MSPS. To keep this band of 60 MHz to 80 MHz in the middle of the first Nyquist Zone, the sampling frequency is 280 MSPS. This signal in frequency domain is shown in Figure 1 ===================== Some of the radio designs use the one down converter stage for converting the 70-MHz IF signal to a lower IF frequency, say 14 MHz 4 -24 mhz с точки зрения максимального динамического диапазона правильное решение ,конечно зависит от динамического ранга смесителя SFDR ADC падает с частотой ============ 3.1 processing gain LTC 2107 210 msps Fin 30 mhz SFDR 96.8 dbFS Fin 71 mhz SFDR 87 dbFS Fin 14mhz +-10mhz 4-24 mhz SFDR 96.8 mhz SNR Fin 30 mhz 79.7 dbFS + process gain (210/2) /20 mhz = 7 db ...=87 dbFS
milstar: While multiple IF stages can become a source of distortion products and spurious responses, the IC-7700 utilizes Icom’s original image-rejection mixers in a simple double conversion superheterodyne. This reduces distortion and produces a much cleaner audio signal compared to triple or quadruple superheterodyne receivers. https://www.icomamerica.com/en/products/amateur/hf/7700/default.aspx
milstar: https://www.icomamerica.com/en/products/amateur/receivers/r8600/Icom-R8600-QST-product-Review.pdf
milstar: http://www.sherweng.com/table.html Yaesu FT-DX101D 18 bit ADC 15msps 9mhz if 4000$ 10 khz -50mhz Flex6700 pure SDR 250 msps 16 bit ADC 6000 $ 10 khz-50 mhz ICOM RC8600 triple conversion superhet + 14 bit ADC 130 msps in demodulator 10 khz-3 GHZ(!) 2000$-2300$
milstar: Highest performance with a bandwidth appropriate filter right up front after the first mixer. This keeps the undesired strong signals from progressing down stream to the next stages. http://www.sherweng.com/ctu2012/NC0B-CU-2012-6a.pdf
milstar: n addition to the classic communica - tions receiver and spectrum analyzer that monitors specific channels or bands, the R8600 is also a “scanner” radio, where the emphasis is on rapid scanning across wide bandwidths, searching for signals of interest that may have unknown frequencies. https://www.icomamerica.com/en/products/amateur/receivers/r8600/Icom-R8600-QST-product-Review.pdf
milstar: https://docs.wixstatic.com/ugd/af543b_4d316147bdf44a73b1d05974fe0ce01a.pdf
milstar: https://mri-progress.ru/products/all-lists/K5111HB015.pdf russian 200 msps 16 bit
milstar: http://www.ti.com/lit/ds/symlink/ads5485.pdf K5111HB015 analog ads5485 https://mri-progress.ru/products/all-lists/K5111HB015.pdf
milstar: ads5485 https://www.pentek.com/pipeline/23_1/PIPE231.pdf
milstar: https://www.analog.com/en/products/ad9697.html# 14 bit ,1.3 GSPS SFDR 81 dbfs SINAD 62.3 dbfs by 1.36 volt p-p ,1980 mhz 415 $
milstar: AD9467 16 bit 250msps -119$ LTC2107 16 bit 210 msps 99$ 30-70 mhz sfdr 100 db AD9690 14 bit 1 gsps 292$ 985 mhz sfdr 80 db AD9695 14 bit 625 msps 406$ 1000 mhz 1.3 v p-p 85 db 1300 msps 831$ 1980 mhz 1.3 v p0p 81 db AD9697 14 bit 1300 msps 415$ 1980 81 db
milstar: https://www.flexradio.com/flex-6700/ Wideband Frequency Coverage: 30 kHz – 72 MHz; 135 – 165 MHz Receiver Architecture: Direct Digital Sampling ADC Resolution: 16-bits ADC Sampling Rate: 245.76 Msps Spurious and Image Rejection Ratio: 100 dB or better https://www.flexradio.com/documentation-flex6000series/ Flex 6700 QST review https://www.flexradio.com/downloads/flex-6700-flex-6300-review-qst/
milstar: 3.1 Processing Gain When the signal is oversampled a greater number of times than its signal bandwidth, then the processing gain is achieved in addition to the SNR shown in the ADC datasheets. For example, for the ADS4149, at 70 MHz, the SNR will be around 72 dB at the sampling rate of 200 MSPS. For our example of 70 MHz with 20-MHz bandwidth, the signal is oversampled by 10 times with respect to signal bandwidth. Note that with respect to the signal frequency of 70 MHz, it is oversampled only around 3 times. Due to oversampling of 10 times to the bandwidth, system designers get the extra advantage of processing gain in addition to the actual SNR mentioned in the datasheet. For Fs of 200 MSPS, the SNR of 72 dB is for a Nyquist bandwidth of Fs/2, that is, 100 MHz. For the measurement of SNR of the ADC, the noise in the entire band of 100 MHz is considered in this case. The processing gain is achieved by using the following formula: Process Gain = 10 log ((Fs/2)/BW) Where Fs is the sampling Rate; BW is the signal bandwidth; For the oversampling example, BW is 20 MHz, Fs is 200 MHz. If we use the above formula, the processing gain is around 7dB. The total SNR can be calculated using the following formula: SNRtotal = SNRds + Process Gain Where SNRtotal is the total SNR after adding the processing gain and SNRds is the SNR value provided in the datasheet (without the processing gain). SNRtotal is 79 dBFS (72 + 7) using the above formula. 6 3.2 Frequency Plan Flexibility With oversampling, the advantage is the frequency plan. System designers can select the IF frequency location wherever required in the first Nyquist Zone based on the availability of passive filter modules at that frequency and for optimizing selection of ADC front end circuit design in that frequency band. The IF frequencies can always be moved anywhere from DC to Fs/2 frequency, with an eye on keeping the flexibility on the filter design. The second and third harmonics of the 70-MHz IF falls out of the first Nyquist Zone and can be easily filtered in the oversampling case of 200 MSPS sampling rate. Whereas, in the undersampling case, the system designers must plan the filter design in such a way that the HD2 and HD3 impacts are minimal. The ADC input filter design has to take care of this distortion issue in the undersampling case. 3.3 Handling Higher Signal Bandwidths The another inherent advantage of oversampling is the capability of handling higher-signal bandwidths. For the oversampling case of 200 MSPS, the ADC can handle around 100-MHz signal BW. This BW is called Nyquist BW. But as per our example case, the signal BW is only 20 MHz and hence the sampling rate of 56 MSPS will be good enough. For the TI ADC12D1600 ADC, the Nyquist BW is 1600 MHz with a sampling rate of 3200 MSPS. This type ADC is generally used for handling very high signal BWs for radio applications. Designers must make the right sampling rate choice for their specific design. The key thing to remember is keeping the entire signal BW inside a single Nyquist Zone for avoiding the bad aliasing effects and keeping the signal BW in the middle of any particular Nyquist Zone for flexibility in the filter design.
milstar: Since a direct sampling technique folds the signal energy from each zone back into the first Nyquist, there is no way to accurately discriminate the source of the content. As a result, rogue energy can appear in the first Nyquist zone, which will degrade signal-to-noise ratio (SNR) and spurious free dynamic range (SFDR). Spectral issues can potentially plague government and military applications, both for sensing and communications. http://mil-embedded.com/articles/bandwidth-king-aerospace-defense-applications/
milstar: Future ADCs specifically designed for undersampling applications will incorporate the previously discussed techniques in a single-chip designs. These ADCs will be characterized by their wide SFDR at input frequencies extending well above the Nyquist limit, fs /2. The basic architecture of the digital IF receiver is shown in Figure 5.31. The addition of a low-distortion PGA under DSP control increases the dynamic range of the system. IF frequencies associated with 900MHz digital cellular base stations are typically around 70MHz with bandwidths between 5 and 10MHz. SFDR requirements are between 70 and 80dBc. On the other hand, 1.8GHZ digital receivers typically have IF frequencies between 200 and 240MHz with bandwidths of 1MHz. SFDR requirements are typically 50dBc. http://sss-mag.com/pdf/ad5.pdf
milstar: https://www.analog.com/media/en/training-seminars/tutorials/MT-002.pdf
milstar: https://www.analog.com/media/en/training-seminars/design-handbooks/High-Speed-Design-Techniques/Section5.pdf
milstar: Figure 4 shows an application which combines oversampling and undersampling. The signal of interest has a bandwidth BW and is centered around a carrier frequency fc. The sampling frequency can be much less than fc and is chosen such that the signal of interest is centered in its Nyquist zone. Analog and digital filtering removes the noise outside the signal bandwidth of interest, and therefore results in process gain per Eq. 10. Figure 4: Undersampling and Oversampling Combined Results in Process Gain https://www.analog.com/media/en/training-seminars/tutorials/MT-001.pdf
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/AD6688.pdf RF Diversity and 1.2 GHz Bandwidth Observation Receiver 895$ https://www.analog.com/media/en/technical-documentation/data-sheets/AD6674.pdf 385 MHz BW IF Diversity Receiver
milstar: http://www-users.york.ac.uk/~dajp1/Introductions/GSW_Noise_and_IP3_in_Receivers.pdf 200 khz noise reciever noise 9.45 db ,s/n 6 db -121+9.45+6= -105.55 db If we didn’t know what minimum signal-to-noise ratio was required for acceptable performance, all we could do is consider the sensitivity to be the minimum detectable signal MDS), which is the input signal that gives an output signal power equal to the output noise power. Using this definition, the sensitivity would be 6 dB less, at –111.55 dBm.
milstar: then you might think that this would give the entire receiver a very low IP3, since the signal would be so large at this stage. However, if the image filter just before this amplifier gets rid of all the signals except the wanted signal, then there aren’t any other signals left to produce any intermodulation products, and the IP3 of this component can be neglected. http://www-users.york.ac.uk/~dajp1/Introductions/GSW_Noise_and_IP3_in_Receivers.pdf
milstar: Communications: Mars Curiosity is equipped with significant telecommunication redundancy by several means: an X band transmitter and receiver that can communicate directly with Earth, Curiosity can communicate with Earth directly at speeds up to 32 kbit/s https://mars.jpl.nasa.gov/msl/mission/communicationwithearth/data/ Data Rates/Returns The data rate direct-to-Earth varies from about 500 bits per second to 32,000 bits per second
milstar: http://www.arrl.org/files/file/QEX_Next_Issue/Jul-Aug_2013/QEX_7_13_Horrabin.pdf
milstar: Do you need more than one SSB BW Filter? Best if Roofing & DSP bandwidths are equal. More selectivity up front is always desirable. Better shape factor than depending of last IF only. Omni-VII the 455 kHz filters really help total selectivity. Orion & K3 both offer a 1.8 kHz roofing filter. Reduces load on DSP ! Just not as dramatic improvement as on CW http://www.sherweng.com/documents/NC0B-Contest-U-2008-9.pdf
milstar: It is not possible to offer CW bandwidth Roofing Filters at VHF frequencies. It all comes down to fractional bandwidth. A 500-Hz filter at 5 MHz is like a 1-kHz filter at 10 MHz, or a 2 kHz filter at 20 MHz or a 4 kHz filter at 40 MHz & an 8 kHz filter at 80 MHz. FTdx-9000 IF = 40 MHz, 3-kHz reasonable. FT-2000 IF = 70 MHz, “3 kHz” = 7 kHz wide The Orion II and the K3 roofing filters are in the 8 to 9 MHz range, similar to the R-4C at 5 MHz. Narrow filters are no problem here http://www.sherweng.com/documents/NC0B-Contest-U-2008-9.pdf
milstar: https://www.analog.com/media/en/reference-design-documentation/design-notes/DSOL44.pdf
milstar: https://www.aanda.org/articles/aa/pdf/2010/02/aa13335-09.pdf SFDR 112 dbc ltc2208 until 30 mhz
milstar: For example, an rms clock jitter of 200 femtoseconds limits an ADC’s SNR performance to no better than 70 dB at 250 MHz. However, a 1 GHz input signal would need an rms clock jitter of 50 femtoseconds or better to achieve the same SNR performance of 70 dB. https://www.analog.com/en/technical-articles/noise-spectral-density.html
milstar: A high-speed analog-to-digital converter (ADC) typically has the largest noise figure of all components in the receiver signal chain. Its contribution to the system noise figure can be reduced greatly by adding more gain (with a low noise figure) upfront using low-noise amplifiers (LNAs). However, this method cannot be used in a blocking scenario. In the presence of a large in-band interferer or jammer that can’t be filtered out, the gain in the signal chain must be reduced in order to avoid saturation of the ADC input. Therefore, the only way to really improve the receiver noise figure is to improve the noise floor by using a data converter with a better signal-to-noise ratio (SNR), as shown in the example https://www.microwavejournal.com/ext/resources/whitepapers/2015/May-2015/HS-ADC-never-has-enough-SNR_FINAL.pdf?1522090117
milstar: ADS54j60 1 GSPS NSD -158.1 dbfs NF -19.5 db https://www.microwavejournal.com/ext/resources/whitepapers/2015/May-2015/HS-ADC-never-has-enough-SNR_FINAL.pdf?1522090117
milstar: http://www.ti.com/lit/an/slyt090/slyt090.pdf
milstar: An example of a superheterodyne receiver frequency plan for X-band is shown in Figure 2. In this receiver, it is desired to receive between 8 GHz and 12 GHz with a 200 MHz bandwidth. The desired spectrum mixes with a tunable local oscillator (LO) to generate an IF at 5.4 GHz. The 5.4 GHz IF then mixes with a 5 GHz LO to produce the final 400 MHz IF. The final IF ranges from 300 MHz to 500 MHz, which is a frequency range where many ADCs can perform well. https://www.analog.com/en/technical-articles/x-and-ku-band-small-form-factor-radio-design.html# high side injection 200 mhz BW lo1 13.4 ghz -17.4 ghz 1IF 5.4 ghz +-100 mhz 5.3 ghz -5.5 ghz 2 IF 400 mhz +- 100 mhz 300-500 mhz rf x band 8-12 ghz
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/AD9371.pdf https://www.analog.com/media/en/technical-documentation/application-notes/AN-1354.pdf https://www.analog.com/en/analog-dialogue/articles/where-zero-if-wins.html
milstar: The IMD curve in Figure 3 is divided into three regions. For low level input signals, the IMD products remain relatively constant regardless of signal level. This implies that as the input signal increases 1 dB, the ratio of the signal to the IMD level will increase 1 dB also. When the input signal is within a few dB of the ADC full-scale range, the IMD may start to increase (but it might not in a very well-designed ADC). The exact level at which this occurs is dependent on the particular ADC under consideration—some ADCs may not exhibit significant increases in the IMD products over their full input range, however most will. As the input signal continues to increase beyond full-scale, the ADC should function acts as an ideal limiter, and the IMD products become very large. For these reasons, the 2nd and 3rd order IMD intercept points are not specified for ADCs. It should be noted that essentially the same arguments apply to DACs. In either case, the single- or multi-tone SFDR specification is the most accepted way to measure data converter distortion. https://www.analog.com/media/en/training-seminars/tutorials/MT-012.pdf
milstar: https://www.armms.org/media/uploads/what-are-the-dynamic-range--limits-of-rf-adcs.pdf
milstar: Paralleling Amplifiers Improves Signal-to-Noise Performance The benefits of adding amplifiers in parallel are improved SNR and lower voltage noise density. For N amplifiers in parallel, the amplifier noise power is reduced by N and the input referred voltage noise density is reduced by √N. Put another way, each time the number of amplifiers is doubled, the amplifier noise power decreases by 2 and the amplifier's input referred voltage noise density decreases by √2. Note that paralleling amplifiers can only reduce the uncorrelated noise added by the amplifiers; it cannot reduce the noise due to other external noise sources (ex. resistors, sensors, other signal conditioning components, etc. In the two parallel amplifier circuit above, the LT6020's input voltage noise density is reduced from 45nV/√Hz to 32nV/√Hz. The circuit below reveals how the input noise density is reduced for N amplifiers with the LT1028 ultralow 0.85nV/√Hz noise density, precision amplifier.
milstar: https://www.analog.com/en/analog-dialogue/articles/multichannel-a-d-converters.html#
milstar: https://ieeexplore.ieee.org/stamp/stamp.jsp?arnumber=6545284
milstar: https://pdfs.semanticscholar.org/f329/723c8c8f26e74e7a8c0e0bd983cda928de60.pdf
milstar: http://ee.sharif.edu/~mmic/notes/XBand_LNA.pdf
milstar: https://www.qorvo.com/products/p/TGA2512 Qorvo's TGA2512 is a wideband low noise amplifier with AGC amplifier for electronic warfare (EW), electronic counter measures (ECM) and radar receiver or driver amplifier applications. Offering high gain 27 dB typical from 5 - 15 GHz, the TGA2512 provides excellent noise performance with typical midband noise figure of 1.4 dB while the balanced topology offers good return loss typically 15dB. approx 30 $ Qorvo's wide-ranging radar solutions — including land, sea and airborne radar platforms such as the F-15, F-22 and the F-35 — all benefit from proven, highly reliable Qorvo technology. Qorvo's rich heritage supporting global defense and commercial needs is unmatched. Qorvo radar products connect and protect defense forces, commercial and defense aircraft, ships, satellites and other assets globally. Our products monitor global threats, track criminals, assess storm conditions, and coordinate your airspace. Qorvo radar products afford customers flexibility in designing systems to fit unique requirements. Airborne radar platforms such as the F-15, F-22 and the F-35 all benefit from proven, highly reliable Qorvo technology. A variety of shipboard and ground-based radar platforms also use Qorvo's high-performance portfolio of products and technologies. Whether engagement is through foundry or standard products, Qorvo offers full transmit/receive (T/R) solutions that span frequencies from DC to 100 GHz with world-class power, efficiency, low noise figure and RF signal controls. As a top supplier for the defense and aerospace industry, Qorvo, through its foundry in Richardson, TX, is an accredited Category 1A "Trusted Source" by the Department of Defense and completed the Defense Production Act Title III GaN-on-SiC program. According to the certification, the accreditation of trust expresses the confidence of the DoD Defense Microelectronics Activity (DMEA) and the National Security Agency's Trusted Access Program Office (TAPO) that Qorvo's facility will continue to deliver trusted foundry microelectronic goods and services to end users which meet mission critical needs now and into the future. Read Less KEY FEATURES TARGET APPLICATIONS
milstar: http://www.planetec.com/product/datasheet/TGA2612.pdf
milstar: https://www.microsemi.com/existing-parts/parts/137227
milstar: https://www.microsemi.com/existing-parts/parts/137225 https://www.microsemi.com/existing-parts/parts/137602 gain 18.5 db oip3 36 db
milstar: https://www.rfmw.com/products/passives/rf-filter?att_1786=10&att_222=5 saw filtr [url=https://www.rfmw.com/datasheets/tai-saw/TB0888A%20_Rev.1.0_.pdf] https://www.rfmw.com/datasheets/tai-saw/TB0888A%20_Rev.1.0_.pdf[/url] 62 mhz -1.5 db bw =1mhz insertion loss 16.5 db -40 db bw -3mhz delay 70 nanosek https://www.rfmw.com/datasheets/tai-saw/TB0941A%20_Rev.1.0_.pdf 70 mhz -1.0 db bw =3.2 mhz insertion loss 24 db -45 db bw =4.08 mhz https://www.rfmw.com/datasheets/tai-saw/TB0229A%20_Rev.3.0_.pdf 70 mhz -1 db bw 12 mhz insertion loss -23 db 40 db bw 13.87 mhz https://www.rfmw.com/datasheets/tai-saw/TB0186B%20_Rev.2.0_.pdf 70 mhz 20 mhz bw insertion loss 20 db 40 db bw 26.5 https://www.rfmw.com/datasheets/tai-saw/TB1001A%20_Rev.1.0_.pdf 70 mhz 1.4 mhz bw ,insertion loss 17 db 40 db bw 2.56 mhz
milstar: https://www.rfmw.com/datasheets/tai-saw/TB0841A%20_Rev.1.0_.pdf 942 mhz 27.5 mhz insertion loss 27 db 30 db bw 30 mhz https://www.rfmw.com/datasheets/tai-saw/TA0522B%20_Rev.1.0_.pdf 1500 mhz insertion loss 2.95 db https://www.rfmw.com/datasheets/tai-saw/TB1030A%20_Rev.1.0_.pdf 974 mhz insertion loss 15.5 db 1db bw 84 mhz 932mhz- 1016 mhz 915 mhz -36 db 1034 -37 db
milstar: https://www.rfmw.com/datasheets/tai-saw/TB0457A%20_Rev.1.0_.pdf 325 mhz 6.4 mhz insertion loss 18.6 db Fc -+5 mhz 42 db https://www.rfmw.com/datasheets/tai-saw/TB1008A%20_Rev.2.0_.pdf 828 mhz 25.5 db insertion loss 1db 14.7 mhz 40 db 18 mhz https://www.rfmw.com/datasheets/tai-saw/TB1215A_Rev.1.0_.pdf 310 mhz insertion 24.5 db 1 db 14.45 mhz 40 db 16.87 mhz https://www.rfmw.com/datasheets/tai-saw/TB0880A%20_Rev.1.0_.pdf 830 mhz insertion loss 24 db 1 db 10.5 mhz 40 db 14.1 mhz attenuation -+ 7.5 mhz 42 db
milstar: https://www.breeeng.com/wp-content/uploads/2018/05/800524_data.pdf 1710 mhz 1701-1719 mhz 1 db insertion loss 1.5 db 1670 mhz ,1750 mhz -60 dbc
milstar: https://pdfs.semanticscholar.org/416c/18f0066f2a339ce97cc8aad3e3c68b239270.pdf 25 db improvement of ltc2208 with digital correction
milstar: litc2208 360-420 mhz from 60 dbfs untill 85 dbfs SFDR
milstar: http://www.microwavefilter.com/rfmicrowave/RF-PDF/capabilitiescatalog.pdf
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/HMC8191.pdf 66$ IIP3 23 db
milstar: https://www.markimicrowave.com/Assets/DataSheets/MT3L-0113H.pdf?v=012419 https://www.markimicrowave.com/Assets/DataSheets/MT3L-0113HSM.pdf 120 $ IIP3 31 db 165 $ https://www.markimicrowave.com/Assets/DataSheets/MT3-0113HCQG.pdf?v=020819
milstar: Important simplifications result from selecting the sampling frequency fs to be equal to 4 fc [1][2]. ====================== The quadrature sinusoids can then be reduced to the trivial sequences {1, 0, -1, 0, . . .} and {0, -1, 0, 1, . . .}, eliminating the need for digital multipliers or the synthesis of the quadrature signals. http://accelconf.web.cern.ch/Accelconf/p95/ARTICLES/RPQ/RPQ02.PDF
milstar: https://www.tek.com/blog/what%E2%80%99s-your-iq-%E2%80%93-about-quadrature-signals%E2%80%A6
milstar: https://www.ll.mit.edu/sites/default/files/page/doc/2018-05/21_1_7_Eshbaugh.pdf
milstar: https://www.renesas.com/eu/en/www/doc/datasheet/hsp50016.pdf Digital Down Converter
milstar: y down converting and centering the band of interest at DC. The conversion is done by multiplying the input data with a quadrature sinusoid. https://www.renesas.com/eu/en/www/doc/datasheet/hsp50016.pdf
milstar: DDCs convert a real, time domain signal into a complex one, centered at baseband. The process of frequency conversion is achieved by mixing – or multiplying – the input signal with a digital sinusoid at the center of the bandwidth of interest. This creates copies of the signal of interest centered around zero, and also at twice the sinusoid frequency. http://www.ni.com/example/31525/en/
milstar: The NCO, sometimes called a local oscillator generates digital samples of two sine waves precisely offset by 90 degrees in phase creating sine and cosine signals [8], [10], [11], (See Figure 2). It uses a digital phase accumulator (adder) and sine/cosine look-up tables. The digital samples out of the local oscillator are generated at a sampling rate exactly equal to the ADC sample clock frequency, fs. Since the data rates from these two mixer input sources are both at the ADC sampling rate, fs, the complex mixer output samples at fs. http://www.iosrjournals.org/iosr-jece/papers/Vol.%2011%20Issue%206/Version-4/B1106040513.pdf
milstar: https://radioprog.ru/post/415
milstar: http://ptgmedia.pearsoncmg.com/images/9780137027415/samplepages/0137027419.pdf Richard Lyons is a consulting systems engineer and lecturer with Besser Associates in Mountain View, California. He has been the lead hardware engineer for numerous signal processing systems for both the National Security Agency (NSA) and Northrop Grumman Corp.
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/AD6620.pdf DDC 21$ 14 bit not for new design https://www.renesas.com/eu/en/www/doc/datasheet/hsp50016.pdf https://www.renesas.com/eu/en/www/doc/application-note/an9401.pdf DDC 16 bit 75 msps
milstar: 2.5.3. Синхронное детектирование https://ozlib.com/831358/tehnika/sinhronnoe_detektirovanie
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/AD6636.pdf
milstar: http://www.geo.uzh.ch/microsite/rsl-documents/research/SARlab/GMTILiterature/PDF/Skolnik90.pdf
milstar: As mentioned in the first page of this chapter, How to Demodulate an AM Waveform, one approach to amplitude demodulation involves multiplying the received signal by a carrier-frequency reference signal, and then low-pass-filtering the result of this multiplication. This method provides higher performance than AM demodulation that is built around a leaky peak detector. However, this approach has a serious weakness: the result of the multiplication is affected by the phase relationship between the transmitter’s carrier and the receiver’s carrier-frequency reference signal. These plots show the demodulated signal for three values of transmitter-to-receiver phase difference. As the phase difference increases, the amplitude of the demodulated signal decreases. The demodulation procedure has become nonfunctional at 90° phase difference; this represents the worst-case scenario—i.e., the amplitude begins to increase again as the phase difference moves away (in either direction) from 90° One way to remedy this situation is through additional circuitry that synchronizes the phase of the receiver’s reference signal with the phase of the received signal. However, quadrature demodulation can be used to overcome the absence of synchronization between transmitter and receiver. As was just pointed out, the worst-case phase discrepancy is ±90°. Thus, if we perform multiplication with two reference signals separated by 90° of phase, the output from one multiplier compensates for the decreasing amplitude of the output from the other multiplier. In this scenario the worst-case phase difference is 45°, and you can see in the above plot that a 45° phase difference does not result in a catastrophic reduction in the amplitude of the demodulated signal. =============================================================================================================================== The following plots demonstrate this I/Q compensation. The traces are demodulated signals from the I and Q branches of a quadrature demodulator. Transmitter phase = 0° Transmitter phase = 45° (the orange trace is behind the blue trace—i.e., the two signals are identical) Transmitter phase = 90° https://www.allaboutcircuits.com/textbook/radio-frequency-analysis-design/radio-frequency-demodulation/understanding-quadrature-demodulation/ Constant Amplitude It would be convenient if we could combine the I and Q versions of the demodulated signal into one waveform that maintains a constant amplitude regardless of the phase relationship between transmitter and receiver. Your first instinct might be to use addition, but unfortunately it’s not that simple. The following plot was generated by repeating a simulation in which everything is the same except the phase of the transmitter’s carrier. The phase value is assigned to a parameter that has seven distinct values: 0°, 30°, 60°, 90°, 120°, 150°, and 180°. The trace is the sum of the demodulated I waveform and the demodulated Q waveform. As you can see, addition is certainly not the way to produce a signal that is not affected by variations in the transmitter-to-receiver phase relationship. This is not surprising if we remember the mathematical equivalence between I/Q signaling and complex numbers: the I and Q components of a signal are analogous to the real and imaginary parts of a complex number. By performing quadrature demodulation, we obtain real and imaginary components that correspond to the magnitude and phase of the baseband signal. In other words, I/Q demodulation is essentially translation: we are translating from a magnitude-plus-phase system (used by a typical baseband waveform) to a Cartesian system in which the I component is plotted on the x-axis and the Q component is plotted on the y-axis. To obtain the magnitude of a complex number, we can’t simply add the real and imaginary parts, and the same applies to I and Q signal components. Instead, we have to use the formula shown in the diagram, which is nothing more than the standard Pythagorean approach to finding the length of the hypotenuse of a right triangle. ============================================================ If we apply this formula to the I and Q demodulated waveforms, we can obtain a final demodulated signal that is not affected by phase variations. The following plot confirms this: the simulation is the same as the previous one (i.e., seven different phase values), but you see only one signal, because all the traces are identical. https://www.allaboutcircuits.com/textbook/radio-frequency-analysis-design/radio-frequency-demodulation/how-to-demodulate-an-am-waveform/
milstar: http://www.ni.com/tutorial/4805/en/ https://www.keysight.com/upload/cmc_upload/All/6-Analysis-of-Baseband.pdf I = 1.059*cos(2π ∗0.624MHz ∗t) Q = −sin(2π ∗0.624MHz ∗t)
milstar: http://www.farnell.com/datasheets/25526.pdf https://www.analog.com/media/en/technical-documentation/application-notes/AN-924.pdf
milstar: https://areeweb.polito.it/didattica/corsiddc/01NVD/ATLCE10/Lessons/ATLCEC51.pdf
milstar: https://datasheets.maximintegrated.com/en/ds/MAX2022.pdf The MAX2022 utilizes an internal passive mixer architecture. This enables a very low noise floor of -173.2dBm/Hz for low-level signals, below about -20dBm output power level. For higher output level signals, the noise floor will be determined by the internal LO noise level at approximately -162dBc/Hz. https://datasheets.maximintegrated.com/en/ds/MAX2023.pdf https://datasheets.maximintegrated.com/en/ds/MAX2021.pdf ♦ 0.06dB Typical I/Q Gain Imbalance ♦ 0.15° I/Q Typical Phase Imbalance ♦ +35.2dBm Typical IIP3 ♦ +76dBm Typical IIP2 ♦ > 30dBm IP1dB ♦ 9.2dB Typical Conversion Loss ♦ 9.3dB Typical NF
milstar: https://www.jlab.org/intralab/calendar/archive01/LLRF/ziomek.pdf
milstar: http://www.ti.com/lit/ds/symlink/trf371125.pdf
milstar: https://indico.desy.de/indico/event/3391/session/5/contribution/97/material/slides/0.pdf IQ sampling Fclock=4FS
milstar: http://airspot.ru/book/file/961/radar_handbook.pdf 2008
milstar: https://mydocx.ru/10-107285.html
milstar: https://apps.dtic.mil/dtic/tr/fulltext/u2/a264466.pdf
milstar: http://news.cqham.ru/articles/detail.phtml?id=519
milstar: https://www.analog.com/en/technical-articles/small-form-factor-satcom-solutions.html Traditional ground station satellite communication systems in the Ka-band have relied on an indoor to outdoor configuration. The outdoor unit includes the antenna and a block downconversion receiver that outputs an analog signal in the L-band. The signal is then passed to the indoor unit, which contains the filtering, digitization, and processing systems. Because there are typically few interfering signals in the Ka-band, the outdoor unit is focused on optimizing the noise figure at the expense of linearity. The indoor to outdoor configuration works well for ground stations, but is difficult to transition into a low size, weight, and power (SWaP) environment. Several new markets are driving the need for small form factor Ka-band access. Unmanned aerial vehicles (UAVs) and dismounted soldiers would benefit from having access to these communication channels. For both UAVs and dismounted soldiers, radio power consumption directly translates to battery life, which translates to mission length. Additionally, legacy Ka-band channels that used to be specific to airborne platforms are now being considered for wider access. This means that the airborne platform that traditionally only needed to downconvert a single Ka-channel may now need to operate on multiple channels. This article will outline the design challenges that are faced in Ka-band, as well as outline a new architecture that will allow for low SWaP radio solution for these applications. Example System with the AD9371
milstar: https://www.renesas.com/kr/en/www/doc/datasheet/isl5416.pdf
milstar: https://www.analog.com/media/en/training-seminars/design-handbooks/Data-Conversion-Handbook/Chapter2.pdf
milstar: https://www.e-ope.ee/_download/euni_repository/file/%203367/Elektrotehnika.zip/42_____.html Начальным фазовым углом, или начальной фазой, называют в электротехнике угол, который прошёл от начала периода до начала наблюдения и который обозначает действительную точку отсчёта (рис.4.4). В начальный момент времени (t = 0), с которого мы начали наблюдение, ЭДС прошла с начала периода 60˚ или π /3. Начальная фаза этой ЭДС 60˚, ω = 0 и начальное значение ЭДС: eo = Em∙sinψ. На рис.4.5 показаны две синусоидальные ЭДС с начальными фазами Ψ1 = 60˚ и Ψ2 = 30˚. Их мгновенные величины: e1 = Em∙sin(ωt +ψ1) и e2 = Em∙sin(ωt +ψ2). Фазовый сдвиг между ними: ψ = ψ1 - ψ2 = 60˚ - 30˚ = 30˚. Рис.4.5. Временная диаграмма двух ЭДС с различными фазовыми углами. По фазе опережает тот синус, период которого начинается раньше, а отстаёт по фазе тот, чей период начинается позже. Т.е. мы можем сказать, что e1 опережает по фазе e2, или e2 отстаёт по фазе от e1. Угол фазового сдвига между напряжением и током обозначается буквой φ (фи). Этот сдвиг фаз имеет смысл, как между их амплитудными, так и нулевыми значениями. Обобщая, получим: φ = ψ1 - ψ2 . φ - угол сдвига фазы; ψ1 - начальная фаза первой синусоидальной величины, напряжения; ψ2 - начальная фаза второй синусоидальной величины, тока. Когда две синусоидальные величины совпадают начальными фазами, то говорят, что они совпадают по фазе. Когда разница между начальными фазами ± π, то говорят, что они в противофазе ============ https://studopedia.ru/12_91248_izmerenie-fazovogo-sdviga.html
milstar: https://ntrs.nasa.gov/archive/nasa/casi.ntrs.nasa.gov/19890010082.pdf NASA (3) Band-pass sampling with digital quadrature mixers (Fig. 3). The input signal is sampled at the rate of 4W samples/sec, and the input samples are then mixed with the samples of reference in-phase and quadrature components and then low-pass filtered to eliminate the double frequency images resulting from the mixing operation. This is performed by using a finite impulse response (FIR) low-pass filter. Since the output of the low-pass filter is bandlimited to 2W, the output is mated (undersampled) by a factor of 2, thereby reducing the subsequent processing rate by 1/2. For bandpass sampling of the input signal it is assumed that the input signal is centered at an odd multiple of the bandwidth frequency. In practice, this is not a restrictive assumption since the IF frequency is normally chosen by the hardware design engineer. (4) Band-pass sampling with digital Hilbert transform (Fig. 4). The input signal is sampled at the rate of 4W samples/sec, the input samples are then Hilbert transformed using a digital Hilbert transformer. The Hilbert transformed sequence and the input sequence are then mixed with the reference in-phase and quadrature components. For band-pass sampling of the input signal it is assumed that the input signal is centered at an odd multiple of the bandwidth frequency. Note that cases (1) and (2) are applications of the ShannonWhittaker theorem, while cases (3) and (4) are obtained from the band-pass sampling theorems discussed below
milstar: 111. Comparison of Sampling Methods In this section the advantages and disadvantages of each of the sampling techniques described in the previous section are considered. (1) I and Q baseband sampling with analog quadrature mixers. Advantages: (a) Since the sampling rate of each channel is 2W samples/sec, this technique requires the slowest possible A/D convertor and processing rate for the recovery of I and Q samples. (b) The analog anti-aliasing filter design for this sampling technique is an ideal low-pass filter with a two-sided bandwidth of 2W. Generally, low-pass analog filters are easier to build than their analog band-pass counterparts. (c) Due to cost considerations, in some applications it is desirable to demodulate the signal directly from RF frequency to baseband with no intermediate stages. In such cases, this sampling method is the only known technique for recovering the in-phase and quadrature components. Disadvantages: (a) It is very difficult to achieve phase and amplitude balance in both in-phase and quadrature reference signals with analog quadrature mixers. Sinsky and Wang have studied this effect when the input signal is simply a sinusoid at frequency fo, and they show that the effect of unmatched phase or gain is to create an image at -fo, where the power of this image is A2/4 for amplitude mismatch, and @/4 for the phase mismatch. Here A and 4 denote the fraction of amplitude imbalance and the phase difference in radians between the two channels, respectively. For example, to provide an image rejection ratio (IRR) of -50 dB due to the phase imbalance, the phase imbalance must be kept under 0.36 deg. In [2] a method is proposed for compensating for these imbalances. In applications where the signal-to-noise ratio is high, the consideration of IRR is not significant since the image power (at -fo) is dominated by the channel noise. (b) The appearance of spurious signals is another problem with analog implementation of quadrature mixers. Normally, high-speed analog mixers are high-speed choppers and produce odd and even harmonics of the carrier frequency. If these harmonics are not properly filtered, they could fold back into the baseband, and severely degrade the performance of the receiver. (c) This technique requires two A/D convertors. ================================= (2) I and Q sampling with analog Hilbert transform. Sometimes referred to as hybrids or 90-deg phase shifters, analog Hilbert transformers are hardly used in practice because of the difficulties inherent in their fabrication. The relative merits and disadvantages of this technique are similar to those of the previous case, except that here additional phase and amplitude imbalance is introduced by the analog Hilbert transformer if it exhibits non-ideal characteristics. ================================ (3) Band-pass sampling with digital quadrature mixers. Advan rages : (a) Since quadrature mixing is done in the digital domain, the phase or amplitude imbalance problems discussed earlier for the baseband satnpling with analog quadrature mixers do not appear here. (b) Low-pass filtering operation is done in the digital domain using FIR filters. These filters are linear phase filters, i.e., they introduce a constant group delay in the output I and Q samples. This is particularly important in applications where ranging or Doppler information must be extracted from the received signal. Digital filters are inherently more robust and flexible than their analog counterparts. The bandwidth of the filter can be easily modified by changing the coefficients of the discrete filter. Furthermore, a special class of filters [3] called half-band filters (HBF) reduces the computational complexity and the processing rate of this sampling technique by a factor of two. (c) Only one A/D convertor is required. (d) If the sampling period is exactly 1/(4 f,), then the reference in-phase and quadrature components reduce to an alternating sequence ============================= Disadvantages: Faster A/D conversion (e& aperture conversion time) is required since the sampling rate is at least at 4W, as opposed to 2W for the baseband sarnpling case. This translates into stricter design requirements for the A/D design parameters, such as the sample and hold, and aperture time. Requires a band-pass anti-aliasing filter prior to band-pass filters are more difficult to fabricate than their low-pass counterparts. A/D conversion. As pointed out earlier, analog band-pass filters are more difficult to fabricate than their low-pass counterparts. https://ntrs.nasa.gov/archive/nasa/casi.ntrs.nasa.gov/19890010082.pdf
milstar: It has been found that band-pass sampling using digital quadrature mixers is the most robust technique for Deep Space Network (DSN) applications. ======================== In deep space applications the signal-to-noise ratio (SNR) is extremely low, eg, the Advanced Receiver performance threshold is at 0 dB with a carrier-to-noise power of -75 dB with a 15 MHz bandwidth. In DSN applications it is necessary to detect telemetry symbols and track signal phase very accurately for ranging and Doppler measurement in order to determine the deep space probe’s position and velocity. Thus, the receiving system cannot tolerate any significant loss due to filtering or phase distortion. Band-pass sampling with digital quadrature mixers can meet these requirements since it does not suffer from the phase and amplitude imbalance which is inherent in I and Q baseband sampling
milstar: d) If the sampling period is exactly 1/(4 f,), then the reference in-phase and quadrature components reduce to an alternating sequence alternating sequence. мат. знакопеременная последовательность.
milstar: https://www.efjohnson.com/resources/dyn/files/75832z342fce97/_fn/Digital_Phase_Modulation.pdf BPSK modulation
milstar: https://descanso.jpl.nasa.gov/DPSummary/Descanso4--Voyager_new.pdf
milstar: https://www.funkshop.com/media/files_public/fb23655a52a4699eab4effe515ebed3f/yaesu-FTDX101D.pdf The Down Conversion type receiver construction is similar to the FTDX5000. The first IF frequency is 9 MHz, and a low noise figure dual gate MOS FET, D-quad DBM (Double Balanced Mixer) with excellent intermodulation characteristics, is implemented in the mixer section. Narrow band SDR configuration makes it possible to use the narrow bandwidth crystal roofing filters that have the sharp shape factor. This achieves the amazing multi-signal receiving performance when confronted with the most challenging on-the-air interference situations. In addition to IF down-conversion, The FTDX101 receivers implement the YAESU legendary powerful RF Front-Ends, outstanding low-noise Local Oscillators, roofing filters with sharp shape factors, and the latest circuit configurations that we carefully selected for all circuit elements. Consequently, the proximity BDR (Blocking Dynamic Range) in the 14 MHz band reaches 150 dB or more, the RMDR (Reciprocal Mixing Dynamic range) reaches 123 dB or more, and the 3rd IMDR (third-order Intermodulation Dynamic Range) reaches 110 dB or more. The Narrow band SDR receiver removes strong out of band signals by using a superheterodyne method, with narrow band roofing filters which significantly attenuates unwanted out of band frequency components, and the wanted signals within the passband are converted to digital by a high resolution 18-bit A/D converter and sent to an FPGA (Field Programmable Gate Array) for signal processing. The FT DX 101 series uses a hybrid SDR configuration that integrates a direct sampling SDR receiver in order to view the entire band status in real time, with the excellent dynamic receiver performance achieved by the narrow band SDR receiver circuit. By using this hybrid SDR design, the overall performance of the entire FTDX101 receiver system is improved. The Direct Sampling SDR driving the real time Spectrum display with its large dynamic range enables the weakest signal to be observed on the display when it appears and the Narrow Band SDR enables that signal to be selected, filtered and then decoded. If there is powerful AM station near your location or in challenging operating situations where there are a lot of strong signals in the band from Contests, DX-pedition activities, those signals outside the pass band can be attenuated by the very effective roofing filter in the front stage of the A/D converter. This reduces the signal load on the A/D converter which is a bottleneck from the viewpoint of the entire receiving circuit. Therefore, interference is reduced making it is possible to continue to operate even under such difficult conditions. https://www.yaesu.com/indexVS.cfm?cmd=DisplayProducts&ProdCatID=102&encProdID=959169DE998192AB87295E90077D740D&DivisionID=65&isArchived=0
milstar: This table compares the performance of two methods of calculating the FFT of an N-point real sequence. Complex FFT refers to using an N-point complex FFT in the standard way, while Real FFT refers to using an N/2-point complex FFT as described in this topic. As expected, the Real FFT method yields superior performance. http://processors.wiki.ti.com/index.php/Efficient_FFT_Computation_of_Real_Input#
milstar: https://pdfs.semanticscholar.org/9cd4/d0cee6c22a65dd6e5ae51c9b6cdbaeb550df.pdf
milstar: it is possible to represent the FFT frequency domain results of strictly real input using only real numbers. Those complex numbers in the FFT result are simply just 2 real numbers, which are both required to give you the 2D coordinates of a result vector that has both a length and a direction angle (or magnitude and a phase). And every frequency component in the FFT result can have a unique amplitude and a unique phase (relative to some point in the FFT aperture). One real number alone can't represent both magnitude and phase. If you throw away the phase information, that could easily massively distort the signal if you try to recreate it using an iFFT (and the signal isn't symmetric). So a complete FFT result requires 2 real numbers per FFT bin. These 2 real numbers are bundled together in some FFTs in a complex data type by common convention, but the FFT result could easily (and some FFTs do) just produce 2 real vectors (one for cosine coordinates and one for sine coordinates).
milstar: https://www.analog.com/media/en/technical-documentation/dsp-book/dsp_book_Ch31.pdf It is painfully obvious from this chapter that the complex DFT is much more complicated than the real DFT. Are the benefits of the complex DFT really worth the effort to learn the intricate mathematics? The answer to this question depends on who you are, and what you plan on using DSP for
milstar: While this is true, it does not give the complex Fourier transform its proper due. Look at this situation this way. In spite of its abstract nature, the complex Fourier transform properly describes how physical systems behave. When we restrict the mathematics to be real numbers, problems arise. In other words, these problems are not solved by the complex Fourier transform, they are introduced by the real Fourier transform
milstar: 1.First, the real Fourier transform converts a real time domain signal, x [n], into two real frequency domain signals, ReX[k ] & ImX[k ]. By using complex substitution, the frequency domain can be represented by a single complex array, X[k]. In the complex Fourier transform, both x [n] & X[k] are arrays of complex numbers. A practical note: Even though the time domain is complex, there is nothing that requires us to use the imaginary part. Suppose we want to process a real signal, such as a series of voltage measurements taken over time. This group of data becomes the real part of the time domain 2. Second, the real Fourier transform only deals with positive frequencies. That is, the frequency domain index, k, only runs from 0 to N/2. In comparison, the complex Fourier transform includes both positive and negative frequencies. This means k runs from 0 to N-1. The frequencies between 0 and N/2 are positive, while the frequencies between N/2 and N-1 are negative. Remember, the frequency spectrum of a discrete signal is periodic, making the negative frequencies between N/2 and N-1 the same as Chapter 31- The Complex Fourier Transform 571 between -N/2 and 0. The samples at 0 and N/2 straddle the line between positive and negative. If you need to refresh your memory on this, look back at Chapters 10 and 12. 3. Third, in the real Fourier transform with substitution, a j was added to the sine wave terms, allowing the frequency spectrum to be represented by complex numbers. To convert back to ordinary sine and cosine waves, we can simply drop the j. This is the sloppiness that comes when one thing only represents another thing. In comparison, the complex DFT, Eq. 31-5, is a formal mathematical equation with j being an integral part. In this view, we cannot arbitrary add or remove a j any more than we can add or remove any other variable in the equation. 4, the real Fourier transform has a scaling factor of two in front, while the complex Fourier transform does not. Say we take the real DFT of a cosine wave with an amplitude of one. The spectral value corresponding to the cosine wave is also one. Now, let's repeat the process using the complex DFT. In this case, the cosine wave corresponds to two spectral values, a positive and a negative frequency. Both these frequencies have a value of ½. In other words, a positive frequency with an amplitude of ½, combines with a negative frequency with an amplitude of ½, producing a cosine wave with an amplitude of one. 5., the real Fourier transform requires special handling of two frequency domain samples: ReX [0] & ReX [N/2], but the complex Fourier transform does not. Suppose we start with a time domain signal, and take the DFT to find the frequency domain signal. To reverse the process, we take the Inverse DFT of the frequency domain signal, reconstructing the original time domain signal. However, there is scaling required to make the reconstructed signal be identical to the original signal. For the complex Fourier transform, a factor of 1/N must be introduced somewhere along the way. This can be tacked-on to the forward transform, the inverse transform, or kept as a separate step between the two. For the real Fourier transform, an additional factor of two is required (2/N), as described above. However, the real Fourier transform also requires an additional scaling step: ReX [0] and ReX [N/2] must be divided by two somewhere along the way. Put in other words, a scaling factor of 1/N is used with these two samples, while 2/N is used for the remainder of the spectrum. As previously stated, this awkward step is one of our complaints about the real Fourier transform. Why are the real and complex DFTs different in how these two points are handled? To answer this, remember that a cosine (or sine) wave in the time domain becomes split between a positive and a negative frequency in the complex DFT's spectrum. However, there are two exceptions to this, the spectral values at 0 and N/2. These correspond to zero frequency (DC) and the Nyquist frequency (one-half the sampling rate). Since these points straddle the positive and negative portions of the spectrum, they do not have a matching point. Because they are not combined with another value, they inherently have only one-half the contribution to the time domain as the other frequencies. signal, while the imaginary part is composed of zeros https://www.analog.com/media/en/technical-documentation/dsp-book/dsp_book_Ch31.pdf https://www.analog.com/media/en/technical-documentation/dsp-book/dsp_book_Ch10.pdf https://www.analog.com/media/en/technical-documentation/dsp-book/dsp_book_Ch12.pdf
milstar: http://publ.lib.ru/ARCHIVES/S/SMIT_Stiven_V/_Smit_S.V..html http://www.autex.spb.su/download/dsp/dsp_guide/ch10en-ru.pdf http://www.autex.spb.su/download/dsp/dsp_guide/ch12en-ru.pdf http://www.autex.spb.su/download/dsp/dsp_guide/ch31en-ru.pdf
milstar: https://cdn.rohde-schwarz.com/pws/dl_downloads/dl_common_library/dl_brochures_and_datasheets/pdf_1/Realtime_FFT_app-bro_en_3606-8308-92_v0100.pdf
milstar: http://lea.hamradio.si/~s53mv/archive/a074.pdf
milstar: https://www3.mpifr-bonn.mpg.de/staff/bklein/FFTS/URSI-FFTS.pdf
milstar: Phase modulation techniques are subdivided into two categories: residual carrier and suppressed carrier. The distinction lies in the presence (residual) or absence (suppressed) of an RF carrier component. Traditionally, space agencies employed the former. However, as data rates have increased and Power Flux Density (PFD) became a problem for Earth orbiting spacecraft, many mission designers began using suppressed carrier modulation. https://deepspace.jpl.nasa.gov/files/phase3.pdf
milstar: https://docplayer.ru/76434324-Drayvery-sverhskorostnyh-acp-na-osnove-svch-mis-shirokopolosnyh-usiliteley.html В статье приводится краткий анализ основных параметров и типов драйверов сверхскоростных ана - лого-цифровых преобразователей (АЦП). Приводится информация о характеристиках серийных АЦП с частотой преобразования до 5,4 ГГц.
milstar: http://www.seas.ucla.edu/brweb/teaching/215D_S2012/fold2.pdf 15Advantages of FoldingzMantains the “one-step” nature of flash conversion.zNo need for interstage DAC, subtractor, residue ampzExtracts information from zero crossingsÆno need for “linear” processingzCompact and efficient 19Folding IssueszFrequency Multiplication at Folding NodeszReduced BW at Folding NodeszDiff Pair Gm MismatchzTail Current MismatchzTrade-Off Between Linearity and Gain
milstar: https://www.ti.com/lit/an/slaa617/slaa617.pdf
milstar: Folding Interpolating ADC 12 bit 10.4GSPS (2*5.2 ) https://www.ti.com/product/ADC12DJ2700 https://www.ti.com/product/ADC12DJ5200RF https://www.ti.com/lit/ds/symlink/adc12dj5200rf.pdf
milstar: For systems that require an arbitrarily narrow bandwidth, the zero-IF architecture is almost always the right solution. However, in applications where arbitrarily wide bandwidth is required, as in instrumentation, radar, and wideband communications, direct RF sampling has long been the goal. In these applications, it is understood that some of the cost and power efficiency afforded by other architectures is traded off for wider system bandwidth. Therefore, when an RF sampling architecture is chosen, it is designed to cover the widest possible bandwidth to ensure overall radio performance. New RF ADCs like the AD9213 are designed to provide ultrafast sample rates beyond 10 GSPS and sample bandwidths more than 8 GHz, enabling direct RF sampling for many applications. Most radio services are allocated less than 75 MHz per band. With a 10 GSPS ADC, the effective utilization of spectrum is less than 2% of the Nyquist bandwidth. In several studies, the power efficiency of direct RF sampling is about ½ that of a zero-IF architecture. To improve overall efficiency in radio applications, RF sampling offers the possibility of sampling more than one band at a time. https://www.analog.com/en/technical-articles/wideband-receiver-for-5g-instrumentation-and-adef.html
milstar: https://sktbes.com/okr.html «Разработка радиационно-стойких КМОП 12 - разрядного сверхбыстродействующего с АЦП с частотой преобразования до 1 ГГц и напряжением питания 1,8 В».
milstar: https://mri-progress.ru/products/bis-i-sbis/spetsialnye-sbis/sbis-16-razryadnogo-atsp/ СБИС К5111НВ015 СБИС 16-разрядного АЦП с частотой дискретизации 200 МГц СБИС 16-разрядного АЦП конвейерного типа с частотой дискретизации 200 МГц изготовлена по КМОП 90-нм технологии и предназначена для аналого-цифрового преобразования диффе- ренциальных аналоговых сигналов. В микросхеме реализован алгоритм встроенной калибров- ки передаточной характеристики. Функциональный аналог ADS5485 фирмы Texas Instruments.
milstar: https://mri-progress.ru/products/catalog/#page/32
milstar: https://www.ridgetopgroup.com/wp-content/uploads/2015/06/PB_RGADC-12B-2G-RH.pdf 12 bit 2 gsps SiGE 0.13 micron (4 interleaved)
milstar: a Tektronix TADF-4300 module featuring a SiGe-based 12.5 GSps 8-bit ADC the new SiGe-based technology will provide an ideal platform for radar, SIGINT, and EW applications. These ADCs, for example, deliver the best speed and Effective Number of Bits (ENOB) currently available from a commercial device. An additional advantage of SiGe-based devices is their low latency, an important feature for bandwidth-sensitive EW applications. . The new SiGe-based generation of ADCs is delivering the next big performance leap, doubling bandwidth speeds up to 12 GSps. For EW applications, the benefit is straightforward: The higher sample rates and associated bandwidth ensure better spectrum coverage and improved Probability Of Intercept (POI) for signals of interest. In addition, the performance of these 8-bit parts surpasses off-the-shelf 10-bit ADCs in terms of Spurious Free Dynamic Range (SFDR). SiGe-based ADCs/DACs double COTS Electronic Warfare processing performance David Jedynak Curtiss-Wright Defense Solutions New ADC and DAC technology based on Silicon-Germanium (SiGe) promises unprecedented levels of functionality and capability for demanding signal processing applications. These new devices, which bring the advantages of SiGe to rugged deployed military systems for the first time, can deliver 2x the performance of currently available ADC/DAC devices, establishing a new class of processing performance for defense and aerospace applications. When deployed on open architecture platforms utilizing OpenVPX COTS boards with latest-generation FPGAs, the new SiGe-based technology will provide an ideal platform for radar, SIGINT, and EW applications. New levels of performance These types of EW applications require a balance between speed and resolution. Compared to earlier designs, these new SiGe-based ADCs/DACs, supplied by vendors such as Tektronix, feature higher sample rate performance. They leverage high-performance data conversion techniques to optimize device performance characteristics such as calibration, power, and signal/noise ratios. These ADCs, for example, deliver the best speed and Effective Number of Bits (ENOB) currently available from a commercial device. An additional advantage of SiGe-based devices is their low latency, an important feature for bandwidth-sensitive EW applications. Until recently, COTS ADC devices on the market have topped out at 3 GSps at 8 bits of resolution. In the past few years though, we’ve begun to see devices that can perform at up to 6 GSps at 8 bits. The new SiGe-based generation of ADCs is delivering the next big performance leap, doubling bandwidth speeds up to 12 GSps. For EW applications, the benefit is straightforward: The higher sample rates and associated bandwidth ensure better spectrum coverage and improved Probability Of Intercept (POI) for signals of interest. In addition, the performance of these 8-bit parts surpasses off-the-shelf 10-bit ADCs in terms of Spurious Free Dynamic Range (SFDR). SFDR is a measure of the performance of the ADC, and higher SFDR ensures improved identification of signals of interest in a crowded spectral environment. Typically, a first pass of the spectrum segment is done at high bandwidth to pull in as much data as possible to obtain areas of interest to analyze, after which a higher-resolution, lower-bandwidth solution is leveraged to focus on specific targets. As warfighters see a far greater range of the spectrum, more lives are saved and mission success probability is increased because of faster, more accurate identification of threats and improved response options. With this new generation of ADCs and DACs, EW system designers get increased bandwidth with sufficient resolution. It’s a win-win with high-quality signal identification and improved immunity from noise that supports real-time analysis of larger amounts of data. While it’s possible to obtain ADCs that operate at 14- to 16-bit resolution rates, these devices typically sample in the hundreds of Msample range, far below the 12 GSps rates at 8 bits now reachable. SiGe-based ADCs/DACs also deliver lower power performance (as measured in Watt/GHz). In addition to their higher speed and lower power, these ADCs/DACs also offer reduced leakage current and less sensitivity to temperature fluctuation, which becomes more critical in EW electronics as process architectures shrink. Faster I/O devices meld with OpenVPX and FPGAs These faster ADCs and DACs can be readily built into rugged open architecture OpenVPX-based EW systems using FPGAs to perform high-speed algorithm processing in the digital domain; this paradigm minimizes the need for performing downconversions or other filtering stages that would typically be handled in an external analog tuner logic, slowing down performance and requiring additional on-board components that use valuable board real estate and add unwanted heat. The new ADC/DAC components can be deployed on OpenVPX hosts so that the system designer has the flexibility to swap out different front-end configurations as required while maintaining a common back-end and software interface to the FPGA to address different types of applications. An example of an OpenVPX board that delivers the latest generation of devices is Curtiss-Wright’s rugged CHAMP-WB-DRFM 6U card set, combining a Tektronix TADF-4300 module featuring a SiGe-based 12.5 GSps 8-bit ADC and a 12 GSps 10-bit DAC (Figure 1), on a Xilinx Virtex-7 FPGA-based 6U VPX card, the CHAMP-WB http://mil-embedded.com/articles/sige-based-warfare-processing-performance/
milstar: High Performance Data Converters for Medical Imaging Systems by Anton Patyuchenko https://www.analog.com/en/analog-dialogue/articles/high-performance-data-converters-for-medical-imaging-systems.html# Digital Radiography Computed Tomography Positron Emission Tomography Magnetic Resonance Imaging Ultrasonography Here is a list of products ideal for the various medical imaging modalities mentioned in this article. ADAS1256: This highly integrated analog front end incorporates 256 channels with low noise integrators, low-pass filters, and correlated double samplers that are multiplexed into a high speed, 16-bit ADC. It is a complete charge-to-digital conversion solution designed for DR applications that can be directly mounted on a digital X-ray panel. For discrete DR systems, the 18-bit PulSAR® ADC AD7960 offers 99 dB of SNR and a 5 MSPS sampling rate to deliver unmatched performance to meet requirements for the highest dynamic range both in noise and in linearity. The 16-bit, dual-channel AD9269 and 14-bit, 16-channel AD9249 pipeline ADCs offer sampling rates of up to 80 MSPS and 65 MSPS, respectively, to enable high speed fluoroscopy systems. ADAS1135 and ADAS1134: These highly integrated 256- and 128-channel data acquisition systems are comprised of low noise, low power, low input current integrators, simultaneous sample-and-hold devices, and two high speed ADCs with a configurable sampling rate and resolution of up to 24 bits with excellent linearity performance to maximize image quality for CT applications. AD9228, AD9637, AD9219, and AD9212: These 12- and 10-bit multichannel ADCs with sampling rates from 40 MSPS to 80 MSPS are optimized for outstanding dynamic performance and low power to meet PET requirements. AD9656: This 16-bit quad pipeline ADC offers a conversion rate up to 125 MSPS and is optimized for outstanding dynamic and low power performance for conventional and direct digital conversion MRI system architectures. AD9671: This 8-channel integrated receiver front end is designed for low cost and low power medical ultrasound applications featuring a 14-bit ADC with up to 125 MSPS. Each channel is optimized for a high dynamic performance of 160 dBFS/√Hz and low power of 62.5 mW in continuous wave mode for applications where a small package size is critical.
milstar: Производительность современной мини-фабрики составляет не десятки и сотни тысяч пластин в месяц, как на фабрике массового производства узкой номенклатуры продукции, а примерно 500 пластин ежемесячно. ############################################# Потребности российского рынка микроэлектроники могут обеспечить, по некоторым оценкам, три-четыре мини-фабрики. ############################################################# При этом их продукция будет конкурентоспособна на мировом рынке контрактного производства. Кроме того, при соблюдении некоторых условий изделия будут востребованы в сфере космического приборостроения, авионики, атомной промышленности и в других областях, где применяются электронные устройства высокой надежности. Еще одно направление – развитие универсальных мини-фабрик как современной производственной базы для нанотехнологических центров коллективного пользования, где наряду с инновацион-ными разработками можно проводить обучение и переподготовку высококлассных научных и производственных кадров. При создании современной мини-фабрики в России следует принимать во внимание, что производство изделий малой серийности и широкой номенклатуры должно быть очень гибким, с низкими эксплуатацион-ными расходами. Для этого необходимо выполнить ряд условий. Использование наноимпринтной литографии вместо традиционной фотолитографии в глубоком ультрафиолете (EUV) позволит существенно (в разы) снизить затраты на оборудование и эксплуатационные затраты, повысить рентабельность проекта. Кроме того, модернизация существующих в России межотраслевых центров изготовления фотошаблонов даст возможность оперативно наладить производство шаблонов для наноимпринтной литографии. Технологический маршрут кристального производства или производства СБИС на общей пластине с использованием наноимпринтной литографии позволяет обеспечить размеры топологии 45 нм и ниже с достаточно высоким коэффициентом выхода годных (табл.3). В лабораторных условиях минимальный размер элемента, полученного методом наноимпринтной литографии, уже сейчас достигает 7–8 нм и менее[2]. ###################################################################################### http://www.electronics.ru/journal/article/4973 На отечественных мини-фабриках имеет смысл размещать оборудование, ориентированное на обработку 200-мм пластин, поскольку оно достаточно дешевое и компактное. Следует учитывать также, что для снижения затрат по созданию таких производств, важен сам принцип формирования технологических кластеров: при мелкосерийном и многономенклатурном производстве на первый план выходит не производительность, а оптимальный состав оборудования. Что касается стоимости современной мини-фабрики, то затраты на ее создание под ключ, включая чистые комнаты и инженерные системы обеспечения энергоносителями, составляют, в зависимости от состава и степени универсальности, от 350 до 500 млн. долл. ######################################################################## Срок реализации проекта "с нуля" – 30–36 месяцев, не больше, иначе проект морально устареет до того, как начнет приносить отдачу. Еще один важный (если не определяющий) фактор в пользу реализации подобных проек-тов – уровень квалификации российских специалистов в данной области, хотя для отладки технологии имеет смысл привлекать иностранных специалистов с опытом работы на производствах такого уровня. http://www.electronics.ru/files/article_pdf/4/article_4973_712.pdf
milstar: http://www.sovel.org/spravochnik1/manufacturers/
milstar: Техпроцесс 28 нм на «Микроне» готовы были разработать самостоятельно, не покупая зарубежное оборудование и лицензии, которые для подобной технологии оцениваются в сумму до 7 млрд долларов. Да их, скорее всего, и не удастся купить, отзывались эксперты — технологии такого уровня запрещены к продаже в ряд стран, включая Россию, по политическим причинам. https://www.zelenograd.ru/hitech/v-zelenograde-namereny-postroit-fabriku-chipov-28-nanometrov/ 500 пластин в месяц — такая производительность будущей фабрики 28 нм озвучивалась в презентации НИИМЭ. Для сравнения, плановая производительность линии «Ангстрема-Т», которую предлагали демонтировать ради 28 нм — до 15 тысяч пластин в месяц, недавно заключены контракты о поставках в Китай, которые загрузят её загрузили более чем наполовину. Отечественный рынок для чипов 28 нм тоже весьма невелик. Согласно опубликованному в октябре отчёту J’son & Partners «Анализ потенциала импортозамещения в микроэлектронике: Интегральные схемы 32 нм», доля спроса отечественных потребителей на чипы 28 нм не превышает 3%, и его почти полностью закрывают поставки американских чипов (произведённых, в основном, в ЮВА). «Задачи по импортозамещению должны быть существенно более амбициозны, особенно с учетом продолжающегося быстрого прогресса технологий производства интегральных схем» , — резюмируют составители отчёта.
milstar: An example of an OpenVPX board that delivers the latest generation of devices is Curtiss-Wright’s rugged CHAMP-WB-DRFM 6U card set, combining a Tektronix TADF-4300 module featuring a SiGe-based 12.5 GSps 8-bit ADC and a 12 GSps 10-bit DAC (Figure 1), on a Xilinx Virtex-7 FPGA-based 6U VPX card, the CHAMP-WB. This modular design approach actually provides designers with two levels of modularity or reconfigurability: The first level is the ability to swap out different mezzanines as needed, and the second level is the inherent reconfigurability of the FPGA itself. This serves to benefit today’s cutting-edge EW applications. http://mil-embedded.com/articles/sige-based-warfare-processing-performance/
milstar: https://www.armms.org/media/uploads/p09---andrew-glascott-jones---direct-conversion-to.pdf
milstar: 16 bit 0.25 mkm SiGe ADC high speed ,high SFDR ,SNR https://ieeexplore.ieee.org/stamp/stamp.jsp?tp=&arnumber=5604661&tag=1
milstar: https://www.st.com/content/st_com/en/about/innovation---technology/BiCMOS.html 0.055 mkm SiGE Bicmos
milstar: This paper describes the design of a high-speed 8-bit Analog to digital converter (ADC) used in direct IF sampling receivers for satellite communication systems in a 0.25 μm, 190 GHz SiGe BiCMOS process. A high resolution front-end track-and-hold amplifier (THA), a low impedance reference and interpolation resistive ladder and high resolution comparators enable the ADC to achieve good performance for input frequencies of up to one-quarter of the sampling rate. The final post layout simulated system features an ENOB of 7.2-bits at an input frequency of 3.125 GHz and a sampling rate of 12.5 GS/s with a FOM of 12.9 pJ per conversion. Both DNL and INL are within 0.5 and 1 LSB, respectively Fig. 3 Folding interpolating ADC architecture https://link.springer.com/article/10.1007/s10470-009-9422-7
milstar: https://www.st.com/content/st_com/en/about/innovation---technology/BiCMOS.html 0.055 mkm SiGE Bicmos
milstar: Созданием первой российской приемопередающей базовой станции для обеспечения работы сетей формата 5G занимаются сотрудники Национального исследовательского университета «Московский институт электронной техники» (НИУ МИЭТ). Исследования ведутся по нескольким направлениям, и к настоящему моменту специалисты уже проработали технологии управления средствами связи программно-конфигурируемых сетей, получения и обработки сигналов множественного MIMO, методы сетевого взаимодействия. Как сообщили в МИЭТ, разработчики нацелены на создание технологий, сокращающих суммарные задержки при передаче и обработке пакетных данных до 1 миллисекунды и меньше. Технологии связи нового поколения 5G предполагают создание сетей с повышенной пропускной способностью, что даст возможность пользователям получать мультимедийный контент максимально быстро и в наилучшем качестве. По предварительным оценкам, создание каждой базовой станции 5G-связи обойдется примерно в три миллиона рублей. Предполагается, что испытаниями и производством станций, разработанных специалистами МИЭТ, будет заниматься Уральское производственное предприятие «Вектор». Напомним, что в соответствии с программой «Цифровая экономика», сотовая связь формата 5G появится до 2022 года в пяти крупнейших мегаполисах страны, а еще через два года сети пятого поколения должны охватить все российские города с населением более миллиона человек. Источник: www.innoros.ru
milstar: http://www.eecg.toronto.edu/~sorinv/papers/az_jssc_sept19.pdf
milstar: http://www.apissys.com/views/media_produit/datasheets/11/AF202-0.pdf
milstar: http://mil-embedded.com/articles/high-speed-drive-design-next-generation-satcom-systems/ An example of a fully digital SATCOM system designed to handle S-band signals was recently developed by a leading SATCOM provider. (Figure 1.) The system uses the Curtiss-Wright CHAMP-WB-DRFM OpenVPX module, which combines both 12 Gsps ADCs and DACs and a Xilinx Virtex-7 FPGA
milstar: https://www.spiedigitallibrary.org/conference-proceedings-of-spie/10562/105625U/High-speed-high-frequency-electro-photonic-ADC-for-space-enabled/10.1117/12.2296202.full?SSO=1
milstar: http://sss-mag.com/pdf/ad4.pdf
milstar: https://www.researchgate.net/publication/325598727_Broadband_photonic_ADC_for_microwave_photonics-based_radar_receiver
milstar: https://www.sandia.gov/radar/imagery/index.html https://www.sandia.gov/radar/video/index.html https://www.sandia.gov/radar/publications/index.html
milstar: The Interstellar H2020 Project Overview The Interstellar project is funded by the EU Commission and Teledyne e2v is leading the development of two data converters to help bridge the RF world. These are an Analog-to-Digital (ADC) converter and a Digital-to-Analog (DAC) converter. The Interstellar project is a consortium led by Teledyne e2v and supported by Thales Alenia Space, Airbus Defence and Space and the Franhofer Institute. The total budget for the project is 7.3 million Euros and the EU has contributed 6.2 million Euros of this. Teledyne e2v is investing even further into the project to drive the progresses of the data converter technology. The data converters The first device developed under the Interstellar project is a four-channel ADC named EV12AQ600. With sampling speeds up to 6 GSPs, the device offers ultra-wide input bandwidth, flexibility and high-speed serial outputs. The second device to be developed under the Interstellar project will be a multi-channel DAC, reconstructing beyond 6 GSPs it offers multi-Nyquist output bandwidth, configurable modes and high-speed serial inputs. https://www.teledyne-e2v.com/products/semiconductors/adc/ev12aq600/ The most advanced and versatile quad-core, multi-channel ADC The first 12-bit ADC to feature a Cross Point Switch (CPS), the EV12AQ600 can operate its four cores simultaneously, independently or paired, to assign its 6.4 GSps sampling speed across the user’s desired channel count: Quad-channel at 1.6 GSps Dual-channel at 3.2 GSps Single-channel at 6.4 GSps SFDR in 4 channels mode without H2 and H3 harmonics is better than 70 dBFS at -1 dBFS up to 5980MHz. https://www.teledyne-e2v.com/shared/content/resources/File/documents/broadband-data-converters/EV12AQ600/DS%2060S%20218366%20EV12AQ60x%20revA.pdf
milstar: A single-core architecture also has advantages in terms of latency. Fore examples, latencies as low as 3 clock cycles as found with the EV12AS200 ############################################# [2] are very useful in applications such as EW and tracking systems. #################################### https://www.eenewsanalog.com/content/selecting-high-speed-adcs-high-frequency-applications/page/0/2 The performance of the system can be enhanced even further using post processing and real-time techniques, such as integral nonlinearity (INL) correction and using dither to improve SFDR. The shape of the INL curve plays a large part in the harmonic performance of the ADC. By characterizing this INL and using a look-up table (LUT) in the interface FPGA, the INL can be minimized, which brings benefits for the SFDR performance. The look-up table correction is a simple subtraction or addition of the measured INL value for the code. Using this technique has very little impact on the size of the FPGA and no impact on throughput. In some cases, the addition of a LUT for INL correction can improve SFDR by 10dB. The SFDR can also be improved by adding an out-of-band noise source to the input data. This can simply be a low-pass-filtered noise generator added to the input signal using a multi-port transformer. This has the effect of moving the input signal around the input scale of the ADC, which reduces the INL effect and improves SFDR (see Figure 4).
milstar: https://pdfs.semanticscholar.org/a868/e2d948b01cef975868088cf23f1f0c2041f2.pdf photonic ADC
milstar: The narrower bandwidth ofthe digitized frequency window (i.e., 1 GHz) was characterizedwith performance of as much as 8.1, 8.0 and 7.4 ENOBs at31.51, 39.49 and 49.49 GHz, respectively. This is, to the best ofthe authors’ knowledge, a full 1 ENOB better than any reportedADC or MDC at 40 GHz and 50 GHz with 1 GHz or higherbandwidth, to date. https://www.osapublishing.org/DirectPDFAccess/9F87BF7B-F585-2B09-EC67A2BA104A493C_315527/jlt-33-11-2256.pdf?da=1&id=315527&seq=0&mobile=no In particular, the photonic assisted ADCs have been shown tobe directly applicable in microwave and millimeter wave down-conversion schemes [3]–[6]. In fact, the last down-conversionapproach has recently been implemented in field trials for afully photonics based radar [7]. In these high frequency sys-tems, carrier frequencies can typically be orders of magnitudegreater than their signal carrying bandwidth. As a result, thecarrier frequency down conversion is useful to reduce the re-quirements of the backend ADC. This, what is often referredto as conventional down-conversion, is usually achieved by alocal oscillator (LO) and a mixer that translate the signal toan intermediate frequency as depicted in Fig. 1(a). However,the reliance on a single LO implicitly assumes the knowledgeabout the exact position of the signal carrier frequency (in or-der to achieve the down-conversion to baseband), which maynot be the case in applications such as RADAR, thus in effectpreventing the detection of signals of arbitrary, or varying car-rier frequency. As a simpler alternative, the down conversioncan be performed directly by means of subsampling (at a ratelower than two times the carrier frequency), effectively takingadvantage of aliasing to down-convert the unknown microwaveor millimeter-wave frequency to the first Nyquist zone, therebyeliminating the need for exact knowledge of the signal (or theLO) position. As stated above, the conceived method is appli-cable only for signals whose bandwidth is smaller than halfof the (sub) sampling rate. The latter method can be put intopractice by means of photonic assisted ADCs that can directlydown convert a signal with high fidelity and wide bandwidthsampling, thus allowing complex digitization steps to be com-pleted in electronics at a lower rate, all the while without theneed for an LO matching the signal carrier frequency. Follow-ing their functionality, these devices are often denoted to as themicrowave-to-digital converters (MDC) [3]
milstar: In particular, the constructed photonic ADC prepro-cessor performance was rigorously characterized at a record of 7.1 (8.0) and 6.7 (7.4) ENOBs at 39.49 and 49.49 GHz,with 5 GHz (1 GHz) bandwidth, as well as with 99 dB·Hz2/3spurious-free dynamic range (SFDR) for the 30–40 GHz range,demonstrating the unprecedented highly linear, high accuracyADC/MDC. These results are compared with previous imple-mentations using a new figure of merit (FOM) for photonicsampled ADC, and they show the highest FOM value for sig-nals up to 50 GHz, to the best of the authors knowledge. https://www.osapublishing.org/DirectPDFAccess/9F87BF7B-F585-2B09-EC67A2BA104A493C_315527/jlt-33-11-2256.pdf?da=1&id=315527&seq=0&mobile=no
milstar: The high speed ADC is one of the primary design considerations in all wideband EW receivers and largely determines system architecture and overall detection and observation capability. Many performance characteristics of the high speed ADC, including sample rate, bandwidth, and resolution, are determining factors on how the rest of the receiver is designed—all the way from the analog RF domain to the DSP requirements. https://www.analog.com/en/technical-articles/28-nm-adcs-enable-next-gen-electronic-warfare-rec-sys.html# This insatiable need for higher sample rate and better resolution has led high speed ADC manufacturers to move to increasingly smaller transistor lithographic nodes (currently 28 nm and 16 nm) that enable these requirements to be achieved without increasing device power consumption. Taking the inherently lower power consumption into consideration makes ADCs on the 28 nm process key enablers in next-generation EW systems with performance and capability requirements previously considered impractical on the ≥65 nm process. The greater sample rates (several GSPS and above) achievable with 28 nm ADCs are one of the most attractive ADC features to most EW system designers, especially for SIGINT, ###################################################### electronic protect (EP), and electronic support (ES) applications. Just as important as ADC bandwidth is the resolution, which allows for greater SNR/SFDR and subsequent ability to detect, observe, and process a target signal. Undersampling beyond the 1st Nyquist is also possible as a result of higher analog input bandwidths.
milstar: https://www.analog.com/en/analog-dialogue/articles/whats-up-with-digital-downconverters-part-1.html
milstar: The TADF-4300 module supports sampling in the 2nd nyquist zone, to analyze signals up to 8 GHz and provides sub-30 ns latency for the ADC and sub 10ns for the DAC. Spurious Free Dynamic Range varies over frequency, and is >58 dB up to 3 GHz and decreases to 45 dB from 3 GHz to 6 GHz signal input frequency. ENOB varies linearly from 7.2 at low frequency, 6.5 at 3 GHz and 6.2 at 6 GHz. https://www.embedded.com/curtiss-wright-launches-high-bandwidth-high-resolution-platform-for-drfm-in-defense-and-aerospace/ https://www.curtisswrightds.com/products/cots-boards/fpga-cards/6u-fpga-processors/champ-wb.html
milstar: ad9213-10g 10gsps 4ghz 7.9 bit ENOB SFDR 60 dbfs 2.6 ghz 8.1 bit ENOB SFDR 65 dbfs
milstar: https://www.edn.com/improving-high-speed-adc-harmonic-performance-for-unbuffered-adcs/
milstar: How fast is fast? The new ADC samples and digitizes spectrum signals at a rate of over 60 billion times per second (60 GigaSamples/sec). That’s fast enough to directly detect and analyze any signal at 30 GHz or below—a range that encompasses the vast majority of operating frequencies of interest https://www.darpa.mil/news-events/2016-01-11 https://www.businesswire.com/news/home/20140915006629/en/Semtech-Ultra-High-Speed-ADC-DAC-Advanced-Digital
milstar: https://www.iqanalog.com/news
milstar: 21102B–BDC–03/13EV10AS152Ae2v semiconductors SAS 20131. Block DiagramThe EV10AS152A combines a 10-bit 3 Gsps fully bipolar analog-to-digital converter chip, driving a fullybipolar DMUX chip with selectable Demultiplexing ratio (1:2) or (1:4). The 5 GHz full power inputbandwidth of the ADC allows the direct digitization of greater than 1 GHz broadband signals in the highIF region, in either L_Band or S_Band ------ but SFDR only 50-54 dbfs ###################### https://www.teledyne-e2v.com/resources/account/download-datasheet/1756
milstar: https://www.teledyne-e2v.com/shared/content/resources/File/documents/broadband-data-converters/EV12AS200A/EV12AS200AZP_DS.pdf 12 but 1.5gsps SFDR only 63-66dbfs
milstar: 14 bit 3 gsps ,but not space grate 0.022 micron 2600 mhz SFDR 70 dbfs input -2dbfs https://www.analog.com/media/en/technical-documentation/data-sheets/AD9208.pdf
milstar: The AD9213 achieves dynamic range and linearity performance while consuming <4.6 W typical. The device is based on an interleaved pipeline architecture and features a proprietary calibration and randomization technique that suppresses interleaving spurious artifacts into its noise floor 12 bit 10 gsps 1000mhz ,sfdr 70 dbfs input -1 dbfs,sinad -55.6 https://www.analog.com/media/en/technical-documentation/data-sheets/ad9213.pdf
milstar: 12 bit single chan 10 gsps 997 mhz -1dbfs sfdr 63 db sinad -53.5 http://www.ti.com/lit/ds/slvsen9/slvsen9.pdf
milstar: Figure 1 illustrates a high level overview of a typical current X-band radar system. Within this system, two analog mixing stages are typically utilized. https://www.analog.com/en/technical-articles/the-demand-for-digital.html# The first stage mixes the pulsed radar return to a frequency of around 1 GHz and the second to an IF in the region of 100 MHz to 200 MHz to enable sampling of the signal using a 200 MSPS or lower ADC, to a resolution of 12 bits or higher. The latest GSPS ADCs are able to provide in excess of 75 dBc SFDR, which is nearly a 20 dBc improvement over devices that have been available in the last decade. This significant leap is even more critical when competing with recent communications infrastructure frequency allocations. The next generation of GSPS converters, such as the AD9625, based on 65 nm or finer CMOS process geometries Radar waveform bandwidths can vary dramatically depending on the application. For example, some synthetic aperture imaging radar waveforms require hundreds of MHz while tracking radars may use wave forms that are tens of MHz wide or even less. For example, consider radar using a 30 MHz bandwidth waveform at an IF of 800 MHz. If this is sampled using an ADC at a sample rate of 2.0 GSPS to a resolution of 12 bits, the output bandwidth of the data would be 1000 MHz, far in excess of the signal bandwidth, and the output data rate from the converter would be 3.0 GBps. If the data is decimated by a factor of 16 using a DDC, not only does the decimation provide some increased noise reduction but the output data rate is reduced to below 625 MBps, which enables data transportation using only a single JESD204B lane!
milstar: https://www.sandia.gov/radar/files/spie_lynx.pdf The Analog-to-Digital Conversion (ADC) is also accomplished by a custom VME board that operates at 125 MHz andprovides 8-bit data. This data can be presummed and otherwise pre-processed before being sent across a RACEway bus to thesignal processor
milstar: https://www.sandia.gov/radar/imagery/index.html
milstar: Resolution 0.1 to 3.0m https://www.sandia.gov/RADAR/files/spie_lynx.pdf The Analog-to-Digital Conversion (ADC) is also accomplished by a custom VME board that operates at 125 MHz and provides 8-bit data. This data can be presummed and otherwise pre-processed before being sent across a RACE way bus to the signal processor http://read.pudn.com/downloads153/doc/673057/A%20Time-Transformation%20Technique.pdf Stretch:ATime-Transfor-mationTechnique Consider an experiment in which the rise timeassociated with a nonrepetitive nanosecond transientis to be mea-sured. If the signal is applied directly to the input of an oscilloscope,inefficient performance and cost results.This due to the factthatan expensive wide-band oscilloscope is required,despite the fact that the duration of the transient is short and the total information content is small.If we had aconvenientway of reducing the bandwidth of the signal by slowing down the waveform before the signal is displayed,we could use an inexpensive instrument.The purpose of this paper is to describe a technique that can be used to provide this function for a wide variety of applications. http://read.pudn.com/downloads153/doc/673057/A%20Time-Transformation%20Technique.pdf
milstar: The latest generation of Teledyne e2v’s ADC features a sampling rate of 5.4GSps (Giga samples per second), input bandwidth of 4.8GHz, low latency (26 clock cycles) ###################### https://www.teledyne-e2v.com/products/semiconductors/adc/ev12as350/ sfdr 1900mhz 58db,snr 53.2db power d. 6.7wt ###################### https://www.teledyne-e2v.com/shared/content/resources/File/documents/broadband-data-converters/EV12AS200A/EV12AS200AZP_DS.pdf Very Low Latency(<5ClockCycles) ######################## Fs 1.5 gsps ,12 bit SFDR 65 db 1600 mhz
milstar: As radio astronomy receiver bandwidth increases, it is nec-essary to increase the speed of analog-to-digital conversion(ADC) as well as the digital signal processing (DSP) in thetelescope’s back end. Otherwise a complex and expensivemixer-filter system is needed, to break the IF bandwidthinto smaller blocks for digital sampling and signal process-ing. Analog-to-digital converters (ADC) capable of samplerates five gigasamples-per-second and faster are now avail-able http://www.atrasc.com/content/stick/papers/ATRASC2018SummaryWeintroubv6.pdf In current wide-band instruments, usable bandwidth blocks∼2 GHz canbe processed digitally, and we envisage a near term futurewhere blocks∼10 GHz might be handled by a single com-pact module. This paper reviews ultra-wideband ADC andDSP technology, and describes examples of wideband pro-cessing in radio astronomy correlators and phased arrays In a sampled data system the width of a single block of pro-cessed bandwidth is set by the ADC sample rate throughthe Nyquist critereon. If the block is narrow, the processormust be preceded by an IF system with many channels; a socalled “hybrid” implementation, which, if large, is likely tobe cost-prohibitive. . FPGAs arenow equipped with asynchronous serializer-deserializer in-put output devices (SERDES). For the newestGTYseries ofSERDES included on the Xilinx Ultrascale+ family input-output data rates in excess of 30 gigabits-per-second (Gbps)is possible. An essential function of the SERDES is todemultiplexthe very high bitrate from the fast ADC chip,so that the FPGA, The numberof bits of conversion is also key, typically, though, singlecore fast devices have relatively few bits. We view four bitsas effectively the minimum requirements for current instru-ment development. In case of correlators four bits delivers99% digital efficiency.
milstar: https://books.google.de/books?id=Plc6pOgteF4C&pg=PA4&lpg=PA4&dq=ew+receiver+design&source=bl&ots=fXa7wCArTW&sig=ACfU3U0COUAdsYURs10h7dZYPMn_q4IXeg&hl=de&sa=X&ved=2ahUKEwiUyK3h15voAhUC3qQKHSWABvgQ6AEwC3oECAcQAQ#v=onepage&q=ew%20receiver%20design&f=false
milstar: As shown in Figure 9, assume that in band 2 we are looking for a 4.5 GHz signal that has a PRI of 1 kHz. Measurements are made at an IF of 3.5 GHz since LO-RF = IF = 8-4.5 = 3.5 GHz. If a 6.5 GHz signal is applied to band 3, its IF also equals 3.5 since LO-RF = 10-6.5 = 3.5 GHz. If this is a strong signal, has a PRI of 1 kHz, and there is switch leakage, a weak signal will be measured and processed when the switch is pointed to band 2. The receiver measures an IF of 3.5 GHz and since the switch is pointed to band 2, it scales the measured IF using the LO of band 2 i.e., LO-IF = RF = 8-3.5 = 4.5 GHz. Therefore, a 4.5 GHz signal is assumed to be measured when a 6.5 GHz signal is applied. Similarly this 6.5 GHz signal would appear as a weak 3.5 GHz signal from band 1 or a 9.5 GHz signal from band 4. https://www.rfcafe.com/references/electrical/ew-radar-handbook/receiver-tests.htm
milstar: https://rd.springer.com/article/10.1007/s10470-009-9422-7 The final post layout simulated system features an ENOB of 7.2-bits at an input frequency of 3.125 GHz and a sampling rate of 12.5 GS/s with a FOM of 12.9 pJ per conversion. Both DNL and INL are within 0.5 and 1 LSB, respectively. The converter occupies 10 mm2 and dissipates 14 W from a 3.3 V supply. The THA and the comparator, as the most critical building blocks affecting the overall performance of the ADC, were implemented experimentally and fully characterized in order to verify their performance and to ascertain the possibility of implementing the complete ADC. The THA occupies an area of 0.5 mm2. It features a SNDR of 47 dB or 7.5-bits ENOB for a 3 GHz bandwidth, a hold time of 21 ps with a droop rate of 11 mV/80 ps and a power dissipation of 230 mW from a 3.3 V supply. The comparator occupies an area of 0.38 mm2 and exhibits an input sensitivity of ±2 mV, an input offset voltage of 1.5 mV, latch and recovery times of 19 and 21 ps, respectively, and a power dissipation of 150 mW from a 3.3 V supply. The experimental results are in good agreement with simulation and expected specifications and indicate that both circuits are suitable for the implementation of the ADC and help to validate that the 8-bit 12.5 GS/s ADC is feasible for implementation in a 0.25 μm SiGe process. The requirement for several down-conversion stages is predicated by the limited bandwidth of the ADC. If a wide-bandwidth ADCs is available, a single down-conversion can be used, as illustrated in Fig. 2, thus improving the linearity of the receiver. Using such an approach, in a satellite communication system, a 64 QAM RF signal in the 10–30 GHz range can be down converted to the IF band of 1–3 GHz using only 1 mixing stage. In this case, the high-speed ADC must have an input bandwidth of 3 GHz with a typical resolution of 8 bits. Higher-order modulation schemes (such as 256 QAM) impose more stringent requirements on the SNR performance of the ADC and thus resolution
milstar: https://iopscience.iop.org/article/10.1086/677799 A 5 Giga Samples Per Second 8-Bit Analog to Digital Printed Circuit Board for Radio Astronomy
milstar: https://www.int.uni-stuttgart.de/en/research/ic/fi-adc/ . Therefore, we use various of such modern BiCMOS technologies for the design of very fast and broadband data converter front-ends with high linearity. The transistors can show transit frequencies of up to 320 GHz at the moment. Am example of such a Track-and-Hold circuit with a conversion rate of 6.4 GS/s and a nominal resolution of 9.5 bit with 2 Vpp differential input voltage range and 50 dBc dynamic range is shown in the following figure. It can be used for parallelization of data converters with lower sampling rates to vastly improve the performance e.g. of radio frequency sensors.
milstar: Photonic ADC (- in russian, Фотоные АЦП) Article (PDF Available) · February 2015 with 553 Reads Cite this publication Rostislav S. Starikov 21.39National Research Nuclear University MEPhI https://www.researchgate.net/publication/280640714_Photonic_ADC_-_in_russian_Fotonye_ACP
milstar: http://waves.phys.msu.ru/files/docs/2015/thesis/Section4.pdf
milstar: Заявленные для истребителя 6-го поколения радиофотонные РЛС создадут в РФ через пару лет Концерн "РТИ" сообщил, что уже начинает производство лазеров для радиофотонных радаров МОСКВА, 9 июля. /ТАСС/. Радиофотонные радиолокационные станции (РЛС) для беспилотников и самолетов появятся в России уже через несколько лет и позволят строить точное радиолокационное изображение цели, сообщили ТАСС в понедельник в пресс-службе концерна "РТИ". Как сообщалось ранее, радиофотонную РЛС планируется, в частности, устанавливать на российский истребитель шестого поколения. Такая станция будет видеть значительно дальше обычной, не будет перегреваться и сможет строить практически фотографическое изображение цели - ее можно будет распознать в автоматическом режиме. В пресс-службе РТИ отметили, что концерн в 2018 году завершает научно-исследовательскую работу по созданию макета радиофотонного локатора (Х-диапазона). По ее итогам "будет определена принципиальная схема построения радиофотонного локатора", добавили в РТИ, что "через несколько лет позволит выпустить образцы сверхлегких и малоразмерных РЛС для беспилотных летательных аппаратов". Такие радары, отмечают в РТИ, "смогут обеспечить "радиовидение", когда получаемое изображение имеет большую детализацию с возможностью распознать тип цели". В концерне добавили, что такие РЛС будут иметь значительно меньшую массу и габариты и потреблять меньше энергии как на беспилотниках, так и на самолетах. Производство элементов РЛС начинается Радиолокационный сигнал в новом виде станций получается за счет преобразования энергии лазера в фотонном кристалле. В РТИ сообщили, что производство лазеров для таких радаров уже начинается. "Концерн "РТИ" запускает первую в России технологическую линию по производству лазеров для создания перспективных радиофотонных радаров", - сказали в пресс-службе. Как отметил генеральный директор РТИ Максим Кузюк, слова которого приводит пресс-служба, "мы в РТИ добиваемся полной локализации производственного цикла интегральных радиофотонных схем для РЛС, чтобы эффективно участвовать в бурно развивающемся направлении, которое может стать гарантом безопасности страны". Концерн уже несколько лет ведет инициативные работы в области радиофотонных локаторов, компания вложила в разработку порядка 200 млн рублей.
milstar: space rel. http://www.ti.com/lit/ds/symlink/adc12dj3200qml-sp.pdf
milstar: http://www.ti.com/lit/an/slaa617/slaa617.pdf MaximizingSFDRPerformancein the GSPSADC:SpurSourcesand Methodsof Mitigation
milstar: The architecture is optimized for RADAR, Electronic Warfare (EW), Signal Intelligence (SIGINT), Radar Warning Receivers (RWR) and Software Defined Radio applications where high temperature range environments are critical – from -54C to +71C. The VPX3-534 is backed up with GPGPU, SBC, networking and even Intel Xeon D architecture DSP product either as board level or full system level solutions including extensive total lifecycle services for a wide lifetime. https://www.curtisswrightds.com/products/cots-boards/io-communication/analog-io/vpx3-534.html?p=10711 3U VPX Kintex UltraScale FPGA 6 Gsps Transceiver The VPX3-534 combines high-speed multi-channel analog IO, user programmable FPGA processing and local processing in a single 3U VPX slot for direct RF wideband processing to 6 Gsps. This card allows for a high performance single slot transceiver with two 6 Gsps 12bit channels, to over 6 GHz instantaneous analog bandwidth, but can also scale to larger system with many channels. An embedded Xilinx Zynq UltraScale+ MPSoC device supports local processing options and well as high level system interfaces. The efficient design of the VPX3-534 provides adequate cooling for solutions requiring high levels of FPGA performance to over 100W card power.
milstar: he combination targets demanding, rugged applications such as electronic warfare, radar, signal intelligence (SIGINT), and electronic countermeasures (ECM). The FMC can handle dual-channel, 8-bit ADC and 10-bit DAC operation at 6.25 Gsamples/s. The frequency conversion blocks of the ADC and DAC can be extended to 70 GHz with 5 GHz of real-time bandwidth. The TADF-4300 is based on Tektronix’s SiGe-based (silicon germanium) data converters. It supports sampling in the second Nyquist zone. Also, it allows the ADC to analyze signals up to 8 GHz and provides sub-30-ns latency for the ADC. The DAC operates at sub-10-ns rates. The spurious free dynamic range (SFDR) varies over frequency. It surpasses 58 dB up to 3 GHz and decreases to 45 dB above 3 GHz. The effective number of bits (ENOB) varies linearly from 7.2 bits at low frequencies to 6.5 bits at 3 GHz and 6.2 bits at 6 GHz. The module exposes the reference clock on the backplane for multichannel synchronization support, allowing multiple board/module combinations to be connected into a more powerful system. The ADC has built-in calibration. The DAC doesn’t need user calibration. The FMC module uses less than 40 W. https://www.electronicdesign.com/technologies/boards/article/21796024/deliver-fast-analog-using-vpx-and-fmc
milstar: https://acqiris.com/wp-content/uploads/2019/05/Acqiris_SA220P_Datasheet.pdf
milstar: Figure 3. Improved frequency plan: The IF harmonics are outside the IF band, which means the image filtering is realizable. https://www.analog.com/en/technical-articles/28-nm-adcs-enable-next-gen-electronic-warfare-rec-sys.html
milstar: system capable of providing up to 6 GHz of instantaneous bandwidth and at least 12 bit signal fidelity, thereby providing over 70 dB of spur-free dynamic range (SFDR), is desired. The bandwidth must be instantaneous, not a scan and tune architecture, in order to capture 100 percent of low-duty cycle signals. The resulting system should allow for the 6 GHz of instantaneous bandwidth to be centered, or tuned anywhere between 3 GHz center frequency (providing DC-6 GHz coverage) or 23 GHz center frequency (providing coverage from 20-26 GHz). ######################################################################## The system should provide real-time recording capability of these signal bandwidths for durations of up to 15 minutes in open file format allowing the files to be ported to a workstation for analysis and manipulation. The current state of the art is a DC-6 GHz bandwidth, 8-bit recording and playback system. Additionally there is a 12-bit system which has 1 GHz of instantaneous bandwidth, with the 1 GHz of bandwidth centered at a frequency tunable from 2 GHz to 26 GHz. That system can be equipped to record signals for over 1 hour but requires substantial hard drive storage. Description: OBJECTIVE: Design and develop an ultra-broadband, high dynamic range receiver system for signal capture, storage, and analysis. DESCRIPTION: Recent technological advances have enabled downconversion and sampling of radio-frequency (RF) signals with high instantaneous bandwidth and fidelity. Applications include recordings of threat signals, jamming waveforms, civilian systems, and other signals of interest for detailed analysis and potential upconversion and playback at RF for replication of these in-the-field collected signals in a laboratory environment. https://www.sbir.gov/node/401673
milstar: https://link.springer.com/article/10.1007/s11045-019-00679-y
milstar: http://www.apissys.com/views/media_produit/datasheets/25/Datasheet_AV129web-0.pdf
milstar: https://safe.nrao.edu/wiki/pub/NGVLA/NgVLAWorkshop/Murden_Analog_Device_Ultra_Wideband_.pdf
milstar: Figure 2. Problematic frequency plan: The IF harmonics are within the IF band—this makes the image filtering difficult. First, the RF image frequency is very closely spaced to the operating band requiring a very difficult filter for image suppression. Second, any IF created from the IF amplification stages are in-band and unable to be filtered by the antialiasing filter. https://www.analog.com/en/technical-articles/28-nm-adcs-enable-next-gen-electronic-warfare-rec-sys.html#
milstar: https://www.annapmicro.com/products/wild-fmc-8a30-adc/
milstar: Free Subscription See the Current Issue Military Embedded Systems Articles Blogs News White Papers Products McHale Report Radar/Electronic Warfare CyberDefense Rpt. Embedded Hardware Embedded Software Signal Processing Unmanned Systems Avionics Design Newsletter Military A.I. …more March 3, 2014 Semtech Announces Ultra-High Speed ADC and DAC for Radar, Advanced Communication Systems Semtech CAMARILLO, Calif., March 3, 2014 -- Semtech Corporation (Nasdaq: SMTC), a leading supplier of analog and mixed-signal semiconductors, today announced that 64GSPS ADC and DAC preliminary cores are available utilizing IBM’s 32nm SOI technology for integration in high performance System on Chip (SoC) solutions. Targeting the requirements of Advanced Communications Systems including the optical communications, radar and electronic warfare markets, these ultra-high speed data converters enable agile operation and concurrent multi-band / multi-beam operation as well as extremely high dynamic performance ideally suited for highly oversampled systems utilizing large instantaneous bandwidth at low power and small areas. The 32nm data converter cores are the first offering in Semtech’s roadmap of data converter cores. The Semtech roadmap includes a family of data converter cores in 14nm FinFET expected to be available end of 2015. “Through leveraging the IBM 32nm SOI process with its unique feature set, we are developing Advanced Cores that we believe are well-suited for meeting the challenges presented by the next step in high performance communications systems such as 400 Gb/s Optical systems and Advanced Radar systems,” said Craig Hornbuckle, Semtech’s Chief Systems Architect. “We are also seeing an expanding range of applications in the existing radio frequency communications marketplace where high-speed digital logic is replacing functions that have been traditionally performed by less flexible analog circuitry." The ADC cores have an area of 4 mm2 and the DAC cores have an area of 2.2 mm2 . The cores include a wide tuning millimeter wave synthesizer enabling the core to tune from 42 to 68 GS/s per channel with a nominal jitter value of 45 femtoseconds root mean square. The full dual-channel 2x64 GS/s ADC core generates 128 billion analog-to-digital conversions per second, with a total power consumption of 2.1 Watts while the dual DAC consumes 1.7 Watts. The cores achieve 5.8 ENOB up to 10 GHz and SFDR greater than 43dB. In addition, the cores contain all necessary BIST and calibration eliminating the need for the user to develop sophisticated production test or mission mode calibration algorithms. http://mil-embedded.com/news-id/?42773=
milstar: As designers use the A/D and D/A converters as bridges between analog and digital data, they also must balance the amount of processing necessary for each realm. "It is always a compromise in the processing you do in the analog part of the world, and processing you do once the data becomes digital," says Andrew Reddig, president and chief technology officer at TEK Microsystems Inc., a high-performance signal processing specialist in Chelmsford, Mass. "It's easy to do lots of manipulations once you get a signal into the digital realm," Reddig explains. "Analog processing is complicated and very expensive." https://www.militaryaerospace.com/computers/article/16721624/military-ad-and-da-converters-come-to-grips-with-a-complex-network-centric-world
milstar: 1.One kind of radar jammer, for example, might have a high priority on speed, at the expense of resolution. Above all, this system may need to detect radar signals quickly so it wastes no time in overwhelming the enemy signal with jamming energy. In this application, it is not so important to characterize the radar signal with fine resolution as it is to detect the radar signal quickly and jam it. ################# 2.Signals intelligence and radio communications, on the other hand, put a priority on high resolution to detect and classify weak signals of interest -- particularly when the desired signals are alongside strong signals or strong sources of noise. ############################################################## In noise and distortion rejection, designers sometimes would like to choose between optimizing for SFDR or SNR. A/D and D/A specialist Analog Devices Inc. in Norwood, Mass., offers the AD 9268 A/D converter that has a dither switch to enable users to choose between optimizing for SFDR and SNR. "It lets the users decide if they want low noise or better spurious performance," says TI's Aparo. ###################### https://www.militaryaerospace.com/computers/article/16721624/military-ad-and-da-converters-come-to-grips-with-a-complex-network-centric-world ################## "We asked one of our customers recently what they want in a perfect world," says TEK Micro's Reddig. "They said take all of the RF [device speed] up to 18 GHz and digitize with enough bits so that everything is digital, and you don't need a tuner or processing at the analog end. A/Ds don't do that yet." ################################# https://www.militaryaerospace.com/computers/article/16721624/military-ad-and-da-converters-come-to-grips-with-a-complex-network-centric-world
milstar: AD9625 12 bit 2.0 GSPS https://www.analog.com/media/en/technical-documentation/data-sheets/AD9625.pdf High performance: exceptional SFDR in high sample rate applications, direct RF sampling, and on-chip reference. SINAD 1000 mhz -58 1800-57.2 dbc ENOB 9.3 9.2 SFDR 80 76 dbc IMD -7dbfs 728.5/731.5 mhz -82.8 dbc price 624.75$
milstar: «Цифра-И1-РК» 1 кв. 2020г. «Разработка и освоение серийного производства 16-разрядного аналого-цифрового преобразователя с частотой преобразования до 500 МГц» ADC08D1500, AD9625, AD9780, AD9691 (ф. Analog Devices) https://sktbes.com/okr.html
milstar: План называется "Новые поколения микроэлектроники и создание электронной компонентной базы". Он, в частности, включает разработку чипов с топологическими нормами 65 (55) нм, 28 нм, 14 нм и твердотельных накопителей данных с топологической нормой 25–30 нм. "Ведомости" отмечают, что и то и другое уже используется зарубежными производителями. Из проекта следует, что закупки оборудования у иностранных компаний не предполагаются. Вложения государства оцениваются в 615 млрд рублей, а внебюджетные средства составят 102,6 млрд рублей. Из них на долю самого "Ростеха" приходится 30 млрд. В соответствии с планом, к 2024 году объем экспорта российской микроэлектроники нового поколения должен достигнуть 20,4 млрд рублей, а к 2030 году – 48,8 млрд. Внутренний рынок к 2024 году может составить 466 млрд рублей.
milstar: 1. РЛС Су-57 двухдиапазонная L and X Band (7.6-8.4 ghz) 2. Диапазон 750-1250 mhz важен не только для более точного обнаружения малозаметных целей но и для всепогодности в условиях морского климата вращающееся aнтенна в диапазоне L 7.5x3 метра для АФАР с полным заполнением (h/2 for 1000 mhz 750-1250 mhz) потребует примерно 1000 аналогово-цифровых преобразователей для РЛС с полностью цифровым формированием луча Naval Research Laboratory Digital Beam Forming Radar #################################################### https://apps.dtic.mil/dtic/tr/fulltext/u2/a403877.pdf AD9625 price 642$ per 1 https://www.analog.com/en/products/ad9625.html#product-overview https://www.analog.com/media/en/technical-documentation/data-sheets/AD9625.pdf можно использовать двойное преобразование частоты 420 mhz and 70 mhz and strech processing https://www.ll.mit.edu/sites/default/files/page/doc/2018-05/21_1_7_Eshbaugh.pdf тогда подойдет AD9467 approx 120$ per 1 +стоимость смесителей и фильтров https://www.analog.com/en/products/ad9467.html mixer https://www.markimicrowave.com/mixers/mixers-products.aspx?utm_source=home&utm_medium=icon&utm_campaign=mixers ########## Naval Research Laboratory Digital Beam Forming Radar https://apps.dtic.mil/dtic/tr/fulltext/u2/a403877.pdf в образцах на линках ниже идеи NRL нереализованны,причина отсутствие на момент разработки ad9625 with SFDR 80 dbc at 1 ghz ,также цена в России тоже возможно , при наличии соответствующей российской аналоговой схемотехники и желания (! не лозунгов -"Мы переходим на цифру") главкома https://www.thalesgroup.com/en/smart-l-mm https://lockheedmartin.com/content/dam/lockheed-martin/rms/documents/ground-based-air-surveillance-radars/FPS-117-fact-sheet.pdf но сейчас вполне возможно реализовать
milstar: Госкорпорация «Ростех» направила в адрес Правительства дорожную карту мероприятий по формированию высокотехнологичной области «Новые поколения микроэлектроники и создание электронной компонентной базы». Согласно документу на развитие российской микроэлектроники потребуется 798 млрд руб. до 2024 г. https://www.cnews.ru/news/top/2020-09-07_rossijskaya_mikroelektronika План, в частности, включает разработку чипов с топологическими нормами 65 (55) нм, 28 нм, 14 нм и твердотельных накопителей данных с топологической нормой 25-30 нм. В феврале 2020 г. куратором высокотехнологичной области «Новые поколения микроэлектроники и создание электронной компонентной базы» был назначен вице-премьер Юрий Борисов, профильным совещательным органом – коллегия Военно-промышленной комиссии, ответственными ведомствами – Минпромторг, Минэкономразвития, Минфин и Минобрнауки. https://www.cnews.ru/news/top/2020-09-07_rossijskaya_mikroelektronika
milstar: https://www.ti.com/lit/ds/symlink/adc12dj5200rf.pdf?ts=1601221923797&ref_url=https%253A%252F%252Fwww.ti.com%252Fdata-converters%252Fadc-circuit%252Fhigh-speed%252Fproducts.html в отличие от ad9625 12 bit SFDR 80dbc at 1000 mhz 2 GSPS 645 $ 12 bit ADC12DJ5200RF - RF-sampling 12-bit ADC with dual-channel 5.2 GSPS or single-channel 10.4 GSPS folding interpolation latency меньше ,SFDR хуже на 10 дб а цена в 4 раза выше
milstar: AD9213 12 bit 10 GSPS ADC ARCHITECTURE The architecture of the AD9213 consists of an input buffered, pipelined ADC. https://www.analog.com/media/en/technical-documentation/data-sheets/ad9213.pdf Table 28. Typical Latency Through the ADC + DSP Blocks (Number of Sample Clocks)1
milstar: The AD9625 architecture includes two DDCs, each designed to extract a portion of the full digital spectrum captured by the ADC. Each tuner consists of an independent frequency synthesizer and quadrature mixer; a chain of low-pass filters for rate conversion follows these components. Assuming a sampling frequency of 2.500 GSPS, the frequency synthesizer (10-bit NCO) allows for 1024 discrete tuning frequencies, ranging from −1.2499 GHz to +1.2500 GHz, in steps of 2500/1024 = 2.44 MHz. The low-pass filters allow for two modes of decimation. A high bandwidth mode, 240 MHz wide (from −120 MHz to +120 MHz), sampled at 2.5 GHz/8 = 312.5 MHz for the I and Q branches separately. The 16-bit samples from the I and Q branches are transmitted through a dedicated JESD204B interface. A low bandwidth mode, 120 MHz wide (from −60 MHz to +60 MHz), sampled at 2.5 GHz/16 = 156.25 MHz for the I and Q branches separately. The 16-bit samples from the I and Q branches are transmitted through a dedicated JESD204B interface.
milstar: Filters become more complex as the transition band becomes sharper, all other things being equal. For instance, a Butterworth filter gives 6-dB attenuation per octave for each filter pole (as do all filters). Achieving 60-dB attenuation in a transition region between 1 MHz and 2 MHz (1 octave) requires a minimum of 10 poles—not a trivial filter, and definitely a design challenge. https://www.analog.com/media/en/training-seminars/tutorials/MT-002.pdf The antialiasing filter design process is started by choosing an initial sampling rate of 2.5 to 4 times fa. Determine the filter specifications based on the required dynamic range and see if such a filter is realizable within the constraints of the system cost and performance. If not, consider a higher sampling rate which may require using a faster ADC. It should be mentioned that sigma-delta ADCs are inherently highly oversampled converters, and the resulting relaxation in the analog anti-aliasing filter requirements is therefore an added benefit of this architecture. The antialiasing filter requirements can also be relaxed somewhat if it is certain that there will never be a full-scale signal at the stopband frequency fs – fa. In many applications, it is improbable that full-scale signals will occur at this frequency. If the maximum signal at the frequency fs – fawill never exceed X dB below full-scale, then the filter stopband attenuation requirement can be reduced by that same amount. The new requirement for stopband attenuation at fs – fabased on this knowledge of the signal is now only DR – X dB. W
milstar: https://www.analog.com/media/en/technical-documentation/tech-articles/Review-of-Wideband-RF-Receiver-Architecture-Options.pdf A Review of Wideband RF Receiver Architecture Options
milstar: https://archive.ll.mit.edu/HPEC/agendas/proc09/Day2/S4_1405_Song_presentation.pdf https://dspace.mit.edu/bitstream/handle/1721.1/119717/1078637048-MIT.pdf?sequence=1&isAllowed=y ad9625 2-2.6 GSPS SFDR 80 dbc at 1000 mhz NLEQ добавит 10 db это уже приличный результат для радара с полностью цифровым формированием луча https://apps.dtic.mil/dtic/tr/fulltext/u2/a403877.pdf в диапазоне L 750-1250 mhz данный диапазон наиболее подходит для климатических условий северной атлантики в Су-57 тоже используется L диапазон и X диапазон (7.6-8.4 ghz or some 1 ghz in 8-12 ghz)
milstar: http://www.syntezmicro.ru/uploads/files/pub/Article27.pdf
milstar: 1. Географические климатические условия Гибель Испанской армады потеря флота Хубилая при попытке высадки в Японию «Божественный ветер» будет бушевать двое суток, сметая всё на своём пути Жесткие требования мореходности ( 9000 т для консервативного проекта, нe с малой площади ватерлинии жесткие требования выбора диапазонов РЛС L 750-1250 mhz и X 7600-8400 mhz 2. РЛС диапазона L лучше в условиях плохой погоды для обнаружения малозаметных низколетящих крылатых ракет требует меньше компонентов для апертуры с полным заполнением, легче удовлетворить требования пo отводу тепла и компоненты более дешевы недостаток большая площадь апертуры,однако этот диапазон используется на фрегатах водоизмещением 4100 тонн AN/SPS-49 7.3 m × 4.3 m https://en.wikipedia.org/wiki/AN/SPS-49 в самолете СУ-57 ( площадь апертуры еще меньше ) 3. для сдвоенной апертуры (как в ФРЕГАТ-М2 ) Источник: http://bastion-karpenko.ru/fregat-m2em-rls/ ВТС «БАСТИОН» A.V.Karpenko с размерами 7.3 m × 4.3 m для АФАР с полным заполнением 1000 mhz h/2 =150 mm потребуется 2*49*30 э=2940 элементов 4. концепция повсеместного(ubiquitous ) радара Naval Research Laboratory https://apps.dtic.mil/dtic/tr/fulltext/u2/a403877.pdf имеет ряд преимуществ пo сравнению с классической АФАР 5. в случае использования супергетеродина с 2 преобразованиями частоты 490 mhz ,70 mhz как в Радаре Cobra Dane https://fas.org/spp/military/program/track/cobra_dane.htm может быть реализована на "отечественных" аналого-цифровых преобразователях https://mri-progress.ru/products/bis-i-sbis/spetsialnye-sbis/sbis-16-razryadnogo-atsp/ СБИС 16-разрядного АЦП конвейерного типа с частотой дискретизации 200 МГц изготовлена по КМОП 90-нм технологии и предназначена для аналого-цифрового преобразования диффе- ренциальных аналоговых сигналов. В микросхеме реализован алгоритм встроенной калибров- ки передаточной характеристики. Функциональный аналог ADS5485 фирмы Texas Instruments. https://mri-progress.ru/products/all-lists/K5111HB015.pdf ############################################################### 6. в случае использования AD9625 12 bit 2-2.6 GSPS SFDR 80dbc возможен отказ от супергетеродина и смесителей RF Sampling NLEQ добавит 10 db to 80 dbc https://www.analog.com/media/en/technical-documentation/tech-articles/Review-of-Wideband-RF-Receiver-Architecture-Options.pdf https://archive.ll.mit.edu/HPEC/agendas/proc09/Day2/S4_1405_Song_presentation.pdf https://dspace.mit.edu/bitstream/handle/1721.1/119717/1078637048-MIT.pdf?sequence=1&isAllowed=y ad9625 2-2.6 GSPS SFDR 80 dbc at 1000 mhz NLEQ добавит 10 db это уже приличный результат для радара с полностью цифровым формированием луча ############################################# 7. AD9625 price 642$ per 1 https://www.analog.com/en/products/ad9625.html#product-overview https://www.analog.com/media/en/technical-documentation/data-sheets/AD9625.pdf The AD9625 architecture includes two DDCs, each designed to extract a portion of the full digital spectrum captured by the ADC. Each tuner consists of an independent frequency synthesizer and quadrature mixer; a chain of low-pass filters for rate conversion follows these components. Assuming a sampling frequency of 2.500 GSPS, the frequency synthesizer (10-bit NCO) allows for 1024 discrete tuning frequencies, ranging from −1.2499 GHz to +1.2500 GHz, in steps of 2500/1024 = 2.44 MHz. The low-pass filters allow for two modes of decimation. A high bandwidth mode, 240 MHz wide (from −120 MHz to +120 MHz), sampled at 2.5 GHz/8 = 312.5 MHz for the I and Q branches separately. The 16-bit samples from the I and Q branches are transmitted through a dedicated JESD204B interface. A low bandwidth mode, 120 MHz wide (from −60 MHz to +60 MHz), sampled at 2.5 GHz/16 = 156.25 MHz for the I and Q branches separately. The 16-bit samples from the I and Q branches are transmitted through a dedicated JESD204B interface. 8. примеры различных РЛС диапазона L Su-57,Cobra Dane ,FPS-117, Gamma DE,AN/SPS-49,Protivnik ,smart-l mm http://ausairpower.net/APA-Rus-Low-Band-Radars.html#mozTocId829681 https://lockheedmartin.com/content/dam/lockheed-martin/rms/documents/ground-based-air-surveillance-radars/FPS-117-fact-sheet.pdf https://www.radartutorial.eu/19.kartei/01.oth/karte003.en.html https://www.thalesgroup.com/en/smart-l-mm
milstar: https://sktbes.com/pv5u-%d0%ba%d0%be%d0%bf%d0%b8%d1%8f.html analog ad9650 1273НВ014 Шифр https://sktbes.com/okr.html Tел: +7 (473) 223-46-79 Факс: +7 (473) 223-66-96 E-mail: sktb@sktbes.ru Политика конфиденциальности
milstar: https://www.ti.com/lit/an/slaa594a/slaa594a.pdf
milstar: A single-core architecture also has advantages in terms of latency. Fore examples, latencies as low as 3 clock cycles as found with the EV12AS200 [2] are very useful in applications such as EW and tracking systems. SiGE 0.18 12 bit 1.5GSPS https://www.eenewsanalog.com/content/selecting-high-speed-adcs-high-frequency-applications/page/0/2
milstar: AD9213 achieves dynamic range and linearity performance while consuming <4.6 W typical. The device is based on an inter-leaved pipeline architecture and features a proprietary calibration ##### SFDR: 70 dBFS at 10 GSPS with −1 dBFS, 1000 MHz input SFDR excluding H2 and H3 (worst other spur): 89 dBFS at 10 GSPS with −1 dBFS, 1000 MHz input LATENCYPipeline Latency 367 Clock cycles Fast Detect Latency (FD) 170 Clock cycles https://www.analog.com/media/en/technical-documentation/data-sheets/ad9213.pdf
milstar: the AD9625, based on 65 nm or finer CMOS process geometries https://www.analog.com/en/technical-articles/the-demand-for-digital.html#
milstar: Radar waveform bandwidths can vary dramatically depending on the application. For example, some synthetic aperture imaging radar waveforms require hundreds of MHz while tracking radars may use wave forms that are tens of MHz wide or even less. https://www.analog.com/en/technical-articles/the-demand-for-digital.html# For example, consider radar using a 30 MHz bandwidth waveform at an IF of 800 MHz. If this is sampled using an ADC at a sample rate of 2.0 GSPS to a resolution of 12 bits, the output bandwidth of the data would be 1000 MHz, far in excess of the signal bandwidth, and the output data rate from the converter would be 3.0 GBps. If the data is decimated by a factor of 16 using a DDC, not only does the decimation provide some increased noise reduction but the output data rate is reduced to below 625 MBps, which enables data transportation using only a single JESD204B lane! This significantly reduces the overall system power required. With the ability to dynamically configure the DDCs or bypass them as needed, new high speed ADCs provide the option of switching between different modes to support power and implement optimized solutions as needed and enable the feature sets needed for cognitive radar applications.
milstar: Electronic Countermeasures systemsneed to analyze wide bandwidths with low signal-to-noise ratios (SNR) to detect critical, time sensitive threats. One way to achieve this is to channelize the wide bandwidth to separate signals of interest from noise and interferers through a filter bank and Fast Fourier Transform (FFT). https://www.intel.com/content/dam/www/programmable/us/en/pdfs/literature/ds/channelizer-jesd204-datasheet.pdf
milstar: Furthermore, the stopband attenuation should be enough to reduce any residual out-of-band signal power to a level invisible to the ADC. You achieve this performance by employing stopband attenuation in excess of the dynamic range of the ADC (Figure 2 ). Assume that the stopband extends to infinity. Applications encountering high noise levels, especially those with high levels of interference occurring close to the edge of the first Nyquist zone, require filters with aggressive falloff. You achieve this performance using high-order filters that typically exhibit poor phase performance and result in dispersion or large group delay. In antialiasing filters, filtering takes place before the time-sampling point, or quantizer; these filters consequently require the use of an analog filter. This requirement is unfortunate because you can more easily and cost-effectively implement aggressive filters in the digital domain. High-order analog filters provide low harmonic distortion and gain flatness to in-band signals. However, the design of these filters is complex because they are too sensitive to gain matching to be practical at more than a few orders of attenuation magnitude. Furthermore, any passband harmonic distortion the filter introduces also produces undesirable signals in the output spectrum of the ADC. Insertion loss might also be important when using passive filters, which increase system noise. https://www.edn.com/designing-antialias-filters-for-adcs/ N-bit ADC: SNR=6.02×N+1.76 dB. For a 14-bit ADC, this approximation requires 80- to 86-dB attenuation with an ideal SNR of approximately 86 dB. A number of standardized filter-transfer functions, including Bessel, Butterworth, Chebyshev, and elliptic, exist. Each has specific characteristics in the passband, transition band, and stopband. Selecting the appropriate topology depends on the most critical performance aspects of a design. Butterworth filters have the flattest passband region and minimal group delays. Chebyshev filters have steeper roll-offs but more passband ripple. Elliptic filters feature the steepest roll-off (Figure 3 ). The figure does not show a Bessel filter, which has a more gradual roll-off but has the key advantage of a linear, or constant, phase response. A number of public-domain tools exist to help developers in the design of a suitable antialiasing filter. Consider an aggressive, eight-pole filter. Inspection shows that the 80-dB-attenuation point occurs at a frequency that is 3.2 times the cutoff frequency, 8 pole Butterworth ################ Note that, by convention, the cutoff frequency is the point at which the filter produces 3 dB of attenuation. You must also consider the phase response of the antialiasing filters. A filtered signal should not see any significant phase alteration. This alteration becomes even worse if phase varies according to input frequency. You normally measure phase variation in a filter in terms of group delay—that is, the derivative of phase with respect to frequency. For a nonconstant group delay, a signal spreads out in time, causing poor impulse response. Dispersion may be an additional worry for system performance. This factor is important in the design of ultrasound systems in which the received-signal phase carries reflection information.
milstar: The Butterworth filter should be chosen if amplitude accuracy is the paramount concern The Chebyshev filter would be the filter of choice if the desired sampling rate is close to the signal bandwidth The Bessel filter is the best choice if pulse fidelity is the primary concern 8th-order filter has a roll-off rate of 48 dB per octave or 160 dB per decade.
milstar: Butterworth filters have fairly good amplitude and transient behavior. The Chebyshev filters improve on the amplitude response at the expense of transient behavior. The Bessel filter is optimized to obtain better transient response due to a linear phase (i.e. constant delay) in the passband. This means that there will be relatively poorer frequency response (less amplitude discrimination). https://www.analog.com/media/en/training-seminars/design-handbooks/Basic-Linear-Design/Chapter8.pdf
milstar: ANALOG FILTERSSTANDARD RESPONSES8.27 such as Williams's (see Reference 2), provide tabulated filter values. These tables classify the filter by where the C denotes Cauer. Elliptical filters are sometime referred to as Cauer filters after the network theorist Wilhelm Cauer. Maximally Flat Delay with Chebyshev Stop Band Bessel type (Bessel, linear phase with equiripple error and transitional) filters give excellent transient behavior, but less than ideal frequency discrimination. Elliptical filters give better frequency discrimination, but degraded transient response. A maximally flat delay with Chebyshev stop band filter takes a Bessel type function and adds transmission zeros. The constant delay properties of the Bessel type filter in the pass band are maintained, and the stop band attenuation is significantly improved. The step response exhibits no overshoot or ringing, and the impulse response is clean, with essentially no oscillatory behavior. Constant group delay properties extend well into the stop band for increasing n. As with the elliptical filter, numeric evaluation is difficult. Williams’s book (see Reference 2) tabulates passive prototypes normalized component values.
milstar: Figure 8.84: Resistor Comparison Chart Figure 8.85: Capacitor Comparison Char CAPACITOR COMPARISON CHART https://www.analog.com/media/en/training-seminars/design-handbooks/Basic-Linear-Design/Chapter8.pdf
milstar: ADC aperture jitter combines with the sampling clock jitterin an rms manner to further degrade the SNR. https://www.analog.com/media/cn/training-seminars/design-handbooks/3689418379346Section5.pdf To explore this further, Figure 1 illustrates a high level overview of a typical current X-band radar system. Within this system, two analog mixing stages are typically utilized. The first stage mixes the pulsed radar return to a frequency of around 1 GHz and the second to an IF in the region of 100 MHz to 200 MHz to enable sampling of the signal using a 200 MSPS or lower ADC, to a resolution of 12 bits or higher. https://www.analog.com/en/technical-articles/the-demand-for-digital.html#
milstar: https://www.analog.com/en/technical-articles/28-nm-adcs-enable-next-gen-electronic-warfare-rec-sys.html A spur analysis using the Keysight Genesys tool can be used to quickly come to the same conclusion. Figure 4 is from the WhatIF frequency planning tool. Figure 4 shows the WhatIF frequency planning tool, where it is set to a 10 GHz operating band, 1 GHz instantaneous bandwidth, high-side LO selection, and a search for up to fifth-order spurious. Spur free zones are illustrated in green and, in this case, fall in the 2nd Nyquist zone of a 3 GSPS ADC.
milstar: RF sampling: Learning more about latency In this post, I’m going to discuss latency in an analog-to-digital converter (ADC). Latency is the time it takes for a signal to travel from point A to point B. In an ADC, latency is how long it takes from the time that an analog input is applied to the time that the digital output word becomes available. Why is latency important? Regardless of the application, latency is a key specification as it determines the response time. For example, data acquisition systems used in military applications are sensitive to the absolute latency, with lower being better. On the other hand, a known latency or deterministic latency is a key requirement for newer techniques like beam forming that is being adopted to improve sensitivity and selectivity in cellular communications systems. Usually expressed in sampling clock cycles, latency naturally includes the time it takes for the ADC core to do the conversion. Conversion time is dependent on the ADC architecture; in a pipelined ADC, latency will depend on the number of internal stages in the pipeline, as opposed to successive-approximation register (SAR) converters that start transmitting the digital-output word within one or two clock periods. https://e2e.ti.com/blogs_/b/analogwire/archive/2017/02/09/rf-sampling-learning-more-about-latency
milstar: Secrecy is an important aspect of military operations. To reduce the probability of intercept or detection, a radar transmission’s form and magnitude is designed in many cases to spread energy over the widest possible frequency range. Low Probability of Intercept (LPI) and Low Probability of Detection (LPD) are classes of radar systems that possess certain performance characteristics that make them nearly undetectable by today’s modern intercept receivers. LPI features prevent the radar from tripping alarm systems or passive radar-detection equipment. To provide resistance to jamming, systems can be architected by intelligently randomizing and spreading the radar pulses over a wide band so there will only be a very small signal on any one band, an approach known as Direct Sequence Spread Spectrum (DS-SS), as seen in Figure 2. Frequency Hop Spread Spectrum (FH-SS) also provides some protection against full band jamming. In these cases, the wide transmission signal consumes bandwidth that is in excess of what is actually needed for the raw signal of interest. Therefore, a wider receiver bandwidth is needed to continue to advance system capability. https://militaryembedded.com/radar-ew/rf-and-microwave/bandwidth-king-aerospace-defense-applications One of the most important factors for success in an LPI system is to use the widest signal transmission bandwidth possible to disguise complex waveforms as noise. This technique conversely provides a higher-order challenge for intercept receiver systems that seek to detect and decipher these wideband signals. Therefore, while LPI and LPD are improved, radar transceiver complexity is increased by mandating a system that can capture the entire transmission bandwidth at once. The ability of an ADC to simultaneously digitize 500 MHz, 1,000 MHz, and even larger chunks of spectrum bandwidth in a single Nyquist band helps provide a means to tackle this system challenge. Moving these bands higher in frequency beyond the first Nyquist of the ADC can be even more valuable. Today’s wideband ADCs offer systems potential for multiple wide Nyquist bands within an undersampling mode of operation. However, using a high order ADC Nyquist band to sample requires strict front-end anti-alias filtering and frequency planning to preventing spectral energy from leaking into other Nyquist zones. ########################################## It also ensures that unwanted harmonics and other lower frequency signals do not fall into the band of interest after it is folded down to the first Nyquist. The bandpass filter (BPF) upstream of the ADC must been designed to filter out unwanted signals and noise that are not near the nominal bandwidth of interest. Since a direct sampling technique folds the signal energy from each zone back into the first Nyquist, there is no way to accurately discriminate the source of the content. As a result, rogue energy can appear in the first Nyquist zone, which will degrade signal-to-noise ratio (SNR) and spurious free dynamic range (SFDR). Spectral issues can potentially plague government and military applications, both for sensing and communications. Wideband communications and sensing systems require extremely high-speed data converters. GSPS ADCs from Analog such as the AD9234, AD9680, and AD9625 not only offer high sample rates for a wider instantaneous bandwidth, but also the ability to sample high frequency inputs above the first Nyquist.
milstar: http://www.panoradio-sdr.de/sdr-hardware/analog-frontend/
milstar: Minimum Detectable Signal (MDS) The minimum receivable power (Pemin) for a given receiver is important because the minimum receivable power is one of the factors which determine the maximum range performance of the radar. The sensitivity level MDS has got a value of 10 -13 Watts ( -100 dBm) for a typical radar receiver. для полосы в 1 герц предел -173.9db в режиме поиска минимум 1 megaherz=60 db , предел -113.9db All receivers are designed for a certain sensitivity level based on requirements. One would not design a receiver with more sensitivity than required because it limits the receiver bandwidth and will require the receiver to process signals it is not interested in. In general, while processing signals, the higher the power level at which the sensitivity is set, the fewer the number of false alarms which will be processed. Simultaneously, the probability of detection of a “good” (low-noise) signal will be decreased. Bandwith One of the most important factor is receiver noise. Every receiver adds a certain amount of noise to its input signal, and radar receiver is no exception. Even with very careful design, noise due to thermal motion of electrons in resistive components is unavoidable. The amount of such thermal noise is proportional to receiver bandwidth. Therefore, bandwidth reduction is a possible solution to the problem of receiver noise. However, if the bandwidth is made too small the receiver does not amplify and process signal echoes properly. A compromise is required. In practice, the receiver bandwidth of a pulse radar is normally close to the reciprocal of the pulse duration. For example, radar using 1 µs pulses may be expected to have a bandwidth of about 1 Mhz. Dynamic Range The receiver system must amplify the received signal without distortion. If a large clutter signal sends the system into saturation, the result is a modification to the spectrum of the signal. This change in spectral content reduces the ability of the signal processor to carry out Doppler processing and degrades the MTI improvement factor. Furthermore, if the receiver enters saturation, then there can be a delay before target detection is restored. In principle, the dynamic range of the receiver must exceed the total range of signal strength from noise level up to the largest clutter signal. In practice dynamic ranges of 80 dB’s or so meets system requirements. The clutter power confirms this requirement as it averages: Rain clutter up to 55 dB Angels to 70 dB Sea clutter to 75 dB Ground clutter to 90 dB. https://www.radartutorial.eu/09.receivers/rx04.en.html
milstar: https://www.phys.hawaii.edu/~anita/new/papers/militaryHandbook/rcvr_sen.pdf RECEIVER SENSITIVITY / NOISE
milstar: АО «ВЗПП-С» (г. Воронеж) Новые российские ПЛИС ПЛИС 5578ТС084 (АЕНВ.431260.422ТУ) предназначена для замены зарубежных микросхем EP3C16 фирмы Altera. Выпускается в 144-выводном металлокерамическом планарном корпусе МК 4248.144–1. · ПЛИС 5578ТС094 (АЕНВ.431260.423ТУ) предназначена для замены зарубежных микросхем EP3C25 фирмы Altera. Выпускается в 304-выводном металлокерамическом планарном корпусе МК 4251.304–2. Основные характеристики новых ПЛИС приведены в таблице. К 2020 году предприятие планирует выпуск новой ПЛИС 5578ТС064 (АЕНВ.431260.402ТУ), предназначенной для замены зарубежных микросхем EP3C55 фирмы Altera: https://www.soel.ru/novosti/2019/novye_rossiyskie_plis/ http://www.vzpp-s.ru/about.htm http://www.vzpp-s.ru/production/catalog.pdf
milstar: https://www.ti.com/lit/an/slaa824/slaa824.pdf SpursAnalysisin the RF SamplingADC
milstar: https://www.ti.com/lit/an/slyt738/slyt738.pdf
milstar: https://niir.ru/produkciya-i-uslugi/nasha-produkciya/bortovaya-apparatura-dlya-kosmicheskix-apparatov-svyazi-i-veshhaniya/maloshumyashhie-usiliteli/ Малошумящие усилители
milstar: The receiver had two down-conversion stages from the S-Band range input (2.7 GHz to 3.7 GHz) to 75 MHz for operation in the second Nyquist zone using a 14-bit ADC sampled at 100MHz. The second Nyquist zone was chosen as a good compromise between ADC frequency response and ease of anti-aliasing filtering. It also enables a frequency plan with better spurious performance. The instantaneous receiver bandwidth was about 15 MHz, set by an anti-aliasing filter placed at the ADC input. https://ieeexplore.ieee.org/document/4250284
milstar: Table IV shows only measured results and allows the following evaluation of the effect of the ADC on the analog segment of the receive chain: The ADC used sets the ST-SFDR performance of the receiver and does not have a significant effect on TT-SFDR, which is noticeably dominant. The ADC increases the system noise figure by design, depending on the gain configuration. The ADC affects the output SNR significantly. The maximum output signal is limited by the ADC saturation, which is well below the saturation (OTOI −10 dB) of the analog portion of the receiver.
milstar: https://www.d.umn.edu/~ihayee/Teaching/ee5765/ece5765_chapter_4_5.pdf Quadrature Amplitude Demodulation
milstar: http://web.mit.edu/6.02/www/f2006/handouts/Lec9.pdf Impact of Phase Misalignment in Receiver Local Oscillator
milstar: Квадратурную (quadrature) модуляцию осуществляют путем передачи по каналу связи в одной и той же полосе частот двух модулированных сигналов, несущие колебания которых ортогональны и квадратурны (их частоты равны, а фазы сдвинуты на 90°, что и поясняет смысл слова «квадратурный»). Временные диаграммы, поясняющие квадратурную модуляцию, Ранее были проанализированы случаи, когда амплитуда и начальная фаза несущего гармонического колебания подвергались модуляции по отдельности. Однако если изменять эти два параметра одновременно, то можно будет передавать сразу два сигнала, модулированных по амплитуде Uu(t) и фазе у(?) Такую модуляцию следовало бы назвать просто амплитудно-фазовой и, очевидно, аналоговой. Однако два модулирующих сигнала модулируют совершенно разные параметры несущего колебания — амплитуду и фазу. https://studme.org/171323/tehnika/kvadraturnaya_modulyatsiya
milstar: Как видно из этого уравнения, фаза сигнала может регулироваться изменением амплитуд I и Q. Итак, цифровую модуляцию несущего сигнала можно осуществить путём изменения амплитуды двух смешиваемых сигналов. Ниже показана блок-схема технических средств, необходимых для генерации сигнала. Блок квадратурного модулятора (Quadrature Modulator) предназначен для смешивания I и Q компонент исходного сигнала (Baseband) с сигналами гетеродина (local oscillator), и дальнейшего сложения друг с другом. Отметим, что фазы сигналов гетеродина также смещены на 90° относительно друг друга. http://media.ls.urfu.ru/510/1322/2969/
milstar: I-Q Quadrature Generator https://www.eecg.utoronto.ca/~kphang/papers/2001/dong_IQphase.pdf
milstar: Characterization of IQ Modulators Counts On Flexible Signal Generator StimulusApplication NoteThe Role of IQ Modulators in MobileTelecommunicationModern mobile telecommunication relies on quadratureamplitude modulation (QAM) to mix digital transmissiondata onto an RF carrier. In QAM, every logical state isassigned to a specific amplitude and phase value. Anexample for QAM is Quadrature Phase-Shift-Keying(QPSK) which encodes four possible symbol bit-pairsinto phase shifts of a sine wave of ±45º and ±135º asshown in Figure 1. Higher order QAM makes it possibleto transmit more bits per symbol. The most commonforms are 16-QAM, 64-QAM, 128-QAM and 256-QAM.An efficient way to generate the modulating (baseband)signal with a specific amplitude and phase is toseparate the signal vector into an in-phase "I"component with phase 0º and a quadrature "Q"component with phase 90º. This reduces the task tomodulating the amplitudes of two sine wave signals. To illustrate, Table 2 lists the I and Q amplitudescorresponding to the four logical states for the QPSKexample discussed here In a next step, the baseband signal is then modulated orup-converted onto the RF carrier with an IQ modulator.These modulators are available as integrated circuitsfrom a number of semiconductor manufacturers. Inprincipal, they consist of two multipliers that are eachdriven by the carrier or local oscillator (LO) frequency,one of them shifted by 90º against the other. Theoutputs of these multipliers are combined to themodulated RF vector signal. https://www.newark.com/pdfs/techarticles/tektronix/Characterization_of_IQ_modulators.pdf
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/55881fb.pdf The LTC®5588-1 is a direct conversion I/Q modulator designed for high performance wireless applications. It allows direct modulation of an RF signal using differential baseband I and Q signals. It supports LTE, GSM, EDGE, TD-SCDMA, CDMA, CDMA2000, W-CDMA, WiMax and other communication standards. It can also be config-ured as an image reject upconverting mixer, by applying 90° phase-shifted signals to the I and Q inputs. The I/Q baseband inputs drive double-balanced mixers. An on-chip balun converts the differential mixer signals to a 50Ω single-ended RF output. F
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/AD6620.pdf he AD6620 is a digital receiver with four cascaded signal-processing elements: a frequency translator, two fixed-coefficient decimating filters, and a programmable coefficientdecimating filter. All inputs are 3.3 V LVCMOS compatible.All outputs are LVCMOS and 5 V TTL compatible.As ADCs achieve higher sampling rates and dynamic range, itbecomes increasingly attractive to accomplish the final IF stageof a receiver in the digital domain. Digital IF Processing is lessexpensive, easier to manufacture, more accurate, and moreflexible than a comparable highly selective analog stage
milstar: Programmable full-scale input range allows trade-off between SNR and SFDR enabling the design of more sensitive radar systems with the ability to acquire and track smaller targets with better accuracy. See chart below. https://www.radiolocman.com/news/new.html?di=67247 2.5 v SNR 76dbf SFDR 100 dbf 100 mhz 160msps
milstar: Broadened SFDR Definition for Wideband Digital Receivers IMD2 crashing the party requires a refreshed definition of the popular receiver FOM instantaneous spurious-free dynamic range (SFDR). SFDR specifies how far down a receiver can detect a small signal when there are multiple larger signals creating IMD spurs. SFDR is specified in dB relative to the large signals. Traditionally, SFDR is defined in terms of IMD3 products, along with NF and processing bandwidth. IMD3-referenced SFDR is derived in many texts, and is sometimes clarified as instantaneous SFDR, which is what we mean in this article.5,6 We’ll call it SFDR3: https://www.analog.com/en/analog-dialogue/articles/sfdr-considerations-in-multi-octave-wideband-digital-receivers.html
milstar: Spectral resolution and sensitivity improve as the FFT bin narrows, which requires increasing N. Longer pulse widths and PRIs require finer resolution to resolve closer spectral lines, which means larger N for proper detection. Increasing N improves spectral line resolution, but only within the IF bandwidth defined by M. If too high a decimation is used, increasing N improves the spectral resolution within the IF BW set by M, but cannot recover the missing signal bandwidth. For example, a pulse train with a pulse width below the minimum receiver pulse width will have a frequency domain sinc function whose main lobe exceeds the decimation bandwidth. Increasing N will help resolve the PRF of the train, but will do nothing to resolve the pulse width; that information is lost. The only fix is to decrease decimation M, increasing the IF bandwidth. Decimation, FFT, and Detection of Pulse Trains EW wideband digital receivers spend a lot of their effort de-interleaving, identifying, and tracking simultaneous incident radar pulse trains. Carrier frequency, pulse width, and pulse repetition interval (PRI) are radar signatures that are critical in figuring out who’s who. Both the time and frequency domain are used in detection schemes.9 An overarching objective is to sense, process, and react to the pulse trains in as short a time duration as possible. Dynamic range is critical because the EW receiver needs to simultaneously track multiple distant targets while being bombarded with high energy jamming pulses. Pulse Train FFT Examples Two pulse train examples are presented. The first represents a pulsed doppler radar exhibiting a very short PW (100 ns) at 10% duty cycle, resulting in very high PRF. The second simulates a pulsed radar exhibiting comparatively longer PW and PRI (lower duty cycle, lower PRF). The following plots and tables illustrate the impact of decimation M and FFT length N on time, sensitivity (noise floor), and spectral resolution. Table 1 summarizes the parameters for easy comparison. The fictional values do not represent specific radars but are nevertheless in a realistic ballpark.10 https://www.analog.com/en/analog-dialogue/articles/sfdr-considerations-in-multi-octave-wideband-digital-receivers.html
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/ad9174.pdf Dual, 16-Bit, 12.6 GSPS RF DAC and Direct Digital Synthesizer
milstar: japanese fabless chip company MegaChips Corp., has announced a 16nm FinFET analog ASIC that integrates a gigabit-class analog-to-digital converter (ADC) and digital-to-analog converter (DAC) to create an analog front end (AFE) for 5G networks and other high-speed applications. The analog ASIC provides a 14-bit, 3.4-Gsps/6.8-Gsps ADC and 12-bit, 3.4-Gsps/6.8-Gsps DAC—in a 16nm SoC that saves power, cost and space when compared to a circuit made of an FPGA and discrete ADCs. The Analog Mega Block (AMB) intellectual property design includes ADCs, DACs, PGAs, IAMPs, PLLs and filters. "Achieving compliance with today’s communications standards is a long and complicated process," said Masahiro Konishi, general manager of MegaChips. "We have a dedicated team of experts focused on AMB development. They work alongside our customers as a virtual R&D team, from the initial design specification through certification and production ramp up." "MegaChips has a long track record of successfully delivering state-of-the-art high-speed ASICs for passive optical networks (PON), home networks (HPNA, G.hn), and access networks (G.fast)," commented Yuji Sakuma, general manager of MegaChips. MegaChips previously added a 28nm AMB with 0.6-Gsps/1.2-Gsps, 14-bit ADC and DAC and a 65nm/130nm AMB with 200-Msps/400-Msps 12-bit ADC and DAC to its analog ASIC IP family. https://www.mwee.com/news/16nm-finfet-analog-asic-integrates-adcdac-5g
milstar: For example, assume an input signal of 30 MHz and arequired SNR of 80 dB. This, in turn, requires a clock withjitter of no more than 531 picoseconds. This assumes anADC SNR that is much better than 80 dB, making jitter thelimiting factor.Clocks and oscillators are often specified in terms ofphase noise rather than timing jitter. The two are similar,and phase noise can be converted to jitter. Raltron offers aWeb-based calculator [2] for this purpose.Wide Dynamic Range DigitizingAs mentioned previously, recording weather radar sig-nals requires a minimum of 105 dB of dynamic range. Sincethe dynamic range of available high speed ADCs is limitedto 90 dB (with processing gain), with further reductionsdown to 80 dB due to the clock source (jitter), a simple ADCis not sufficient.Symtx Inc. has implemented a dual ADC scheme toincrease digitizer dynamic range as shown in Figure 3. Thedesign uses a high-gain channel to process low-level sig-nals and a low-gain channel to process high-level signals,with simultaneous sampling of both channels in parallel. http://www.highfrequencyelectronics.com/Sep08/HFE0908_S_Crean.pdf he gain difference between the high-level and low levelADCs is compensated with an appropriate n-bit left shiftto give the correct scaling. A DSP after the two ADCs thenselects the correct ADC output, adjusts for gain, andmerges the two to create a 20-bit word with the desireddynamic range.The process is essentially an instantaneous AGC whichresponds to the signal amplitude at the input. Since rangebins for weather radars are on the order of 1 microsecond,the DSP operates by scanning the data for each range binto determine the maximum signal amplitude. If this iswithin the maximum level for the high-gain (low-signal-level) ADC, it is used for data collection (to maximize signalresolution). If any sample exceeds this threshold, all data inthe range bin is collected using the low-gain (high-signal-level) ADC
milstar: Все разработанные микросхемы не уступают по характеристикам своим аналогам, а в дальнейшем планируется выйти в более высокочастотную область(X диапазона), с возможным применением технологии SiGe 0.13 БиКМОП. https://mri-progress.ru/publicatsii/%D0%9A%D0%A0%D0%95%D0%9C%D0%9D%D0%98%D0%99-%D0%93%D0%95%D0%A0%D0%9C%D0%90%D0%9D%D0%98%D0%95%D0%92%D0%AB%D0%95%20%20%D0%9A%D0%92%D0%90%D0%94%D0%A0%D0%90%D0%A2%D0%A3%D0%A0%D0%9D%D0%AB%D0%95%20%D0%9C%D0%9E%D0%94%D0%A3%D0%9B%D0%AF%D0%A2%D0%9E%D0%A0%D0%AB%20%D0%98%20%D0%94%D0%95%D0%9C%D0%9E%D0%94%D0%A3%D0%9B%D0%AF%D0%A2%D0%9E%D0%A0%D0%AB.pdf
milstar: http://vita.mil-embedded.com/articles/very-sampling-serial-adcs-embedded-systems/ While the JESD204B standard has simplified multichannel synchronization by using deterministic latency, minimal latency is needed in some applications such as electronic warfare (EW) and radar applications where actions are required immediately after detection. For these applications, the LVDS interface should still be considered, as the JESD204B-compliant data converter’s delay in serializing the data is omitted. However, applications such as radar warning receivers (RWR) or COMINT that are receiver-only applications tolerate the latency brought on by the JESD204B serialization. These applications thus can benefit from the last generations of ADCs driven by the mass market of telecommunication infrastructure, allowing very high-speed sampling and reducing the complexity of the analog part of the system.
milstar: Emerging threats drive RF and microwave component design trends for electronic warfare Story January 14, 2021 https://militaryembedded.com/radar-ew/rf-and-microwave/emerging-threats-drive-rf-and-microwave-component-design-trends-for-electronic-warfare “Frequency-hopping is now more complex, and adversaries are moving as high as 130+ GHz for use in military terrestrial and on-orbit systems,” D’Arcy explains. “Furthermore, there is a need to incorporate more sophisticated digital methods into electronic attack or defense systems, which will require greater speed and efficiency when moving the signal of interest from analog to digital and back.” “This requires advances in gallium nitride (GaN) amplifiers, up- and down-converters, filters, drivers, and exciters.” (Figure 1.) For both high-speed analog-to-digital (ADC) and digital-to-analog (DAC) converters (digitizers), the push is to enable direct sampling by exceeding 20 Gsamples/sec and above with an increasing number of output and input bits,” D’Arcy says. “Of equal importance, due to the ability to defeat systems with measurable processing delay, is the requirement to reduce latency at the converter and the FPGA [field-programmable gate array] that is induced prior to data reaching the digital backbone. Bent pipe or digitally controlled analog still have significant use due to their minimal latency.” To drive this reduction in latency and manage the scale of the greater data, “more processing fabric is being incorporated into the digitizers,” he adds. “This allows for extensive digital decimation and loopback control to be done closer to the antenna for the ADC signal chain. Conversely, fabric to enable digital data expansion and beamforming are being incorporated into the DAC for its related signal chain.” Another design trend emerging is increasing demand from the DoD for trusted RF and microwave solutions, coming as adversaries develop new electronic capabilities. “It’s no longer acceptable to develop a single system that can be fielded for 10 years without regular modernization,” says Ken Hermanny, senior director and general manager of Mercury’s West Caldwell, New Jersey, facility. “We leverage open standards from chip scale to system scale to incorporate the most advanced technologies and make them accessible to our aerospace and defense customers.”
milstar: Yet another trend is dual-purpose solutions. “In the past, we offered banded-solution approaches leveraging our cellular infrastructure devices,” Smith states. “As a key component supplier within the cellular infrastructure market, many of the same devices used for communications also had a dual purpose for electronic warfare. https://militaryembedded.com/radar-ew/rf-and-microwave/emerging-threats-drive-rf-and-microwave-component-design-trends-for-electronic-warfare
milstar: One key similarity between EW and radar requirements is the demand for increased capability within a single transistor. “For radar, the power levels continue to be much higher than requirements for electronic warfare or communications,” Smith notes. “In many cases, the key metric for radar is efficiency – always trying to push the boundaries and achieve as high efficiency as possible. Efficiency also matters within EW, but it’s based on the market bandwidth and integration. While both radar and EW require high-performance solutions in compact SWaP-optimized packaging, Hermanny points out that EW has its own unique challenges: “Unlike radar, where both transmit and receive sides of the system are defined, an electronic warfare system must operate on previously unknown signals,” he explains. For example, an EW system might need to receive an adversary’s radar signal, process it, and retransmit that signal. “Since the electronic warfare system designer can’t predict the frequency of that radar signal, they need to design the electronic warfare system to operate over a very wide range of frequencies,” Hermanny says. “This unknown element requires electronic warfare systems to be dynamically configurable and operate over a very wide frequency range.” https://militaryembedded.com/radar-ew/rf-and-microwave/emerging-threats-drive-rf-and-microwave-component-design-trends-for-electronic-warfare
milstar: Early in the receiver design the A/D operation is chosen. Sampling in the 2nd Nyquist zone has become popular. The primary benefits are that the 2nd IF harmonics produced either in the mixer or in amplifier non-linearities are out of band and can be filtered. Sampling in a higher Nyquist zone produces a digital downconversion and can be quite useful when frequency planning. The primary compromise of IF sampling is the A/D performance degrades as the input frequency increases. This concern must be balanced with other tradeoffs in the overall receiver design. https://www.mwrf.com/technologies/components/article/21845907/receiver-design-considerations-in-digital-beamforming-phased-arrays Peter Delos is lead RF/RFIC engineer for Lockheed Martin Corp. ############################ 16-Bit, 200 MSPS/250 MSPS Analog-to-Digital ConverterData Sheet AD9467 https://www.analog.com/media/en/technical-documentation/data-sheets/AD9467.pdf SFDR at 170 MHz at 250 MSPS 92 dBFS at −1 dBFS 100 dBFS at −2 dBFS = 98 dbc -------------------------------------------------
milstar: Spur Generation +-n Fin +-kFs
milstar: https://neuron.eng.wayne.edu/auth/ece4330/practical_sampling.pdf
milstar: Take a quick numerical example. The AD974 is a 200ksps ADC and let's assume that the highest frequency you want to capture is 75kHz. Ok so we design a low pass filter with 75kHz cut off frequency. With 200kHz sampling frequency, Nyquist is 100kHZ, and the first image is at 150kHz. To maintain accuracy you need a filter which will attenuate any signals at 150kHZ to better than 74dB (in order to maintain a 12bit dynamic range). So filter must roll off approx 70dB in one octave, that's a 23 pole filter you need So you can see that even to sample at frequencies close to Nyquist you need a fairly expensive filter. https://ez.analog.com/data_converters/high-speed_dacs/w/documents/2786/ad974-antialiasing-filter
milstar: Frequency Folding Tool https://www.analog.com/en/design-center/interactive-design-tools/frequency-folding-tool.html
milstar: https://www.analog.com/media/en/training-seminars/design-handbooks/MixedSignal_Sect2.pdf
milstar: https://www.precisionreceivers.com/our-technology/ HDRR technology allows a wideband staring receiver to be built that in sparse signal environments can take a broad snapshot of the entire spectrum with high dynamic range. In dense signal environments a preselector can be switched-in to narrow the bandwidth, improving the spurious performance of the system. Figure 2 is the block diagram of a staring receiver.
milstar: https://aicdesign.org/wp-content/uploads/2018/08/lecture38-150629.pdf
milstar: he corresponding frequency domain representation of the above scenario is shownin Figure 5.4. Note that sampling the analog signal fa at a sampling rate fs actuallyproduces two alias frequency components, one at fs+fa, and the other at fs–fa. Theupper alias, fs+fa, seldom presents a problem, since it lies outside the Nyquistbandwidth. It is the lower alias component, fs–fa, which causes problems when theinput signal exceeds the Nyquist bandwidth, fs/2. https://www.analog.com/media/cn/training-seminars/design-handbooks/3689418379346Section5.pdf
milstar: Figure 9 shows a signal in the second Nyquist zone entered around a carrier frequency, fc, whose lower and upper frequencies are f1 and f2. The antialiasing filter is a bandpass filter. The desired dynamic range is DR, which defines the filter stopband attenuation. ´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´´ https://www.analog.com/media/en/training-seminars/tutorials/MT-002.pdf TRANSITION BAND: f2 TO 2fs-f2 RANSITION BAND: f1 TO fs-f1 CORNER FREQUENCIES: f1, f2
milstar: The CR9052 filter’s pass-band ripple is less than ±0.01 dB (0.1%), and the stop-band attenuation exceeds 90 dB (1/32,000). The FIR filter’s transition band has a steep roll-off (graph below), with the stop-band frequency starting a factor of 1.24 above the pass-band frequency. In comparison, the stop-band frequency of an ideal eight-pole Butter-worth filter with the same ripple and at-tenuation starts a factor of 5.81 above its pass-band frequency https://s.campbellsci.com/documents/us/product-brochures/b_cr9052.pdf
milstar: https://www.analog.com/media/en/training-seminars/design-handbooks/Basic-Linear-Design/Chapter8.pdf
milstar: narrow-band application could effectively use an ADC with poor wideband SFDR. By using an antialiasing filter to reject the frequencies in the red shaded areas, any harmonics or spurs that would otherwise dictate poor SFDR are now filtered out of band. https://www.analog.com/media/en/GLP/Understanding-Spurious-Free-Dynamic-Range-in-Wideband-GSPS-ADCs-MS-2660.pdf
milstar: Coherent Seeker Guided AntishipMissile Performance AnalysisJAMES J. GENOVAIntegrated EW Simulation BranchTactical Electronic Warfare Division Naval Research Laboratory https://citeseerx.ist.psu.edu/viewdoc/download?doi=10.1.1.928.3912&rep=rep1&type=pdf
milstar: https://www.ab4oj.com/sdr/flex/6700notes.pdf ad9457 Flex 6700 test
milstar: The first one from MIT Lincoln Laboratory (MIT/LL), demonstrated an operating photonic architecture that used time-division-demultiplexing (TDDM) techniques(35). Figure 3-1 shows the schematic layout. The mode-locked laser sampled the input RF electronic signal using an E-O modulator. The optical signal was demultiplexed from 500 MS/s to 65 MS/s using a series of switches to de-interleave the data down to data rates which were processed by a series of “slow” electronic ADCs (65 MS/s) with high resolution (12 bits). MIT/LL demonstrated 505 MS/s BW operation with 51 dB SNR allowing 8 bits of resolution and a SFDR of 61 dB(35). Although the BW of 505 MHz was far from the 5 GHz goal, MIT was successful at demonstrating this photonic ADC working on the HAYSTACK Radar (HAX) platform in Massachusetts. This demonstration was noteworthy in demonstrating that photonics can accurately convert an analog signal to a digital signal. https://apps.dtic.mil/dtic/tr/fulltext/u2/a449267.pdf
milstar: https://www.ab4oj.com/sdr/flex/6700notes.pdf ad9467
milstar: https://www.pentek.com/deliver/deliver.cfm?DI=5&FN=PIPE294.pdf
milstar: The super-heterodyne architecture does allow for the filtering of harmonics and IMD2 products created by the device prior to the ADC. https://www.ti.com/lit/ug/tidu767/tidu767.pdf
milstar: https://www.analog.com/media/en/technical-documentation/data-sheets/ad9166.pdf The DAC core is based on a quad-switch architecture, which is configurable to increase the effective DAC core update rate of up to 12.8 GSPS from a 6.4 GHz DAC sampling clock, with an analog output bandwidth of true dc to 9.0 GHz, typically.
milstar: https://sktbes.com/be_developed.html воронеж разработка аналого цифровых преобразователей https://sktbes.com/okr.html
milstar: Москва. 24 марта. INTERFAX.RU - Вице-премьер Юрий Борисов заявил о возможной блокировке экспорта в РФ из США всей высокотехнологичной продукции. "Администрация Байдена с сентября месяца фактически вводит "кокомовские" списки (Координационный комитет по экспортному контролю (КоКом) - международная организация, в эпоху холодной войны составлявшая перечни "стратегических" товаров и технологий, не подлежащих экспорту в СССР и другие соцстраны - ИФ). То есть в Россию по их желанию будет запрещен экспорт всей высокотехнологичной продукции, какой они посчитают нужным", - сказал Борисов в среду на форуме "Госзаказ". https://www.interfax.ru/russia/757577
milstar: re: Убить беспилотник vpk-news https://www.vpk-news.ru/articles/61569 1. ....Важнейшим условием обеспечения стратегической стабильности обороны государства является гарантированное прикрытие стратегических ядерных сил от ударов сил воздушно-космического нападения противника Вадим Юрьевич ВОЛКОВИЦКИЙ генерал-лейтенант, начальник Главного штаба Военно-воздушных сил, заслуженный военный специалист, кандидат военных наук 2. регулярно идут антидиверсионные учения po прикрытию РВСН что предполагает использование противником мини БПЛА с минимальной отражающей способностью летящих с низкой скоростью над лесным массивом 3. стоимость поражения подобных бпла в данном случае без значения 4. Важнейшая задача -обнаружение ,дискриминация и сопровождение 5. при использовании РЛС воздушного базирования за точку отсчета можно взять хорошо описанную РЛС Ирбис Е самолета Су-35 апертура 900 миллиметров , средняя мощность 5 квт , две лампы челнок 2*2.5 kwt дальность обнаружения в идеальных условиях ( угол места 30 градусов и более , отсутствие снега ,дождя ,мешающих отражений и источников помех поставленных противником ) для цели с ЭПР = 2.5 квадратных метра - 350 километров для цели с ЭПР = 0.01 квадратных метра - 90 километров 6. в указанных выше условиях важнейшей одной из важнейших причин сокращения дальности будут мешающие отражения от неподвижного лесного массива для низкоскоростной цели 7. Именно за передачу данных po радиолокации в нижней полусфере Адольф Толкачев получил свой оперативный псевдоним «Sphere 8. сейчас это все не является секретом ,однако требует использование АФАР и высокой вычислительной мощности встроенной вычислительной системы ( embedded system) 3 терафлопса и более Пространственно-временная адаптивная обработка https://www.radartutorial.eu/20.airborne/ab11.ru.html https://www.eetimes.com/radar-basics-part-4-space-time-adaptive-processing/ https://archive.ll.mit.edu/publications/journal/pdf/vol09_no2/9_2spacetime.pdf https://www.intel.com/content/dam/www/programmable/us/en/pdfs/literature/wp/wp-01197-radar-fpga-or-gpu.pdf 9. при реализации одной вычислительной системы важна потребляемая мощность на один гигафлопс традиционно используются FPGA Altera,Xilinx ( и в разработках российского военно-промышленного комплекса ) , может быть специализированный процессор или заказная интегральная схема 10 . РЛС наземного базирования наиболее уместна концепция повсеместной РЛС ( более передовая чем стандартная АФАР ) Ubiquitous Radar Naval Research laboratory https://www.semanticscholar.org/paper/Systems-Aspects-of-Digital-Beam-Forming-Ubiquitous-Skolnik/2cf76259bfcfeff6cc013278024f050f42892f48?p2df Drone Detection and RCS Measurements with Ubiquitous Radar https://radar2018.org/abstracts/pdf/abstract_74.pdf 11. это потребует использования аналого-цифрового преобразователя в каждом элементе антенны при использовании наиболее уместного для данной цели диапазона L 750-1250 mgz антенны 3 метра*9 метров и полном заполнении из расчета h/2 15 sm 20*60 = 1200 аналого-цифровых преобразователей AD9625 стоимость каждого 1069 $ https://www.analog.com/media/en/technical-documentation/data-sheets/AD9625.pdf 12. конечно будут использоваться и средствa радиоэлектронной борьбы http://www.ntc-reb.ru/index.html http://www.ntc-reb.ru/director.html АО «НТЦ РЭБ» «ПОЛЕ-21Э» http://www.ntc-reb.ru/pole.html Унифицированные модули радиопомех пространственно распределенной системы прикрытия объектов от прицельного применения высокоточного оружия #################### example 1 GHz l-band and 3 GHz s-band rf sources then atmospheric attenuation due to oxygen and water vapor in the atmosphere are on the order of (all data taken from "Radio Wave Propagation", Nat'l Defense Research Committee, Stephen Attwood): ~0.005 dB/km for l-band and ~0.0065 dB/km for s-band, this would mean that over a 400 km distance the l-band set would experience a one-way attenuation of ~2 dB while s-band set would experience a loss of ~2.6 dB... ####################### this attenuation corresponds to a radiated rf energy drop of around 37% for l-band and 45% for s-band over the 400 km distance... not a tremendously huge difference but it still shows that l-band would experience less of a loss due to atmospheric attenuation as compared to s-band... in inclement weather (ie. rain) two effects have to be considered, attenuation (similar to that due to atmospheric effects), and backscatter (ie. clutter) due to raindrops scattering the rf energy... for attenuation due to rainfall, the actual losses also depend on the rainfall rate (with it's attendant effect on raindrop size distribution), hence taking for example 4 mm/hr rainfall a 1 GHz l-band set would experience 1.08 x 10^-4 dB/km attenuation (yes that is 10 to the minus 4 power, it's that small), while a 3 GHz s-band set would experience 1.19 x 10^-3 dB/km attenuation (note that the total attenuation due to rainfall would be only over the distance the rf energy radiated into in which the rainfall is present)... here the diff is a factor of around 11 times greater attenuation per km for s-band than for l-band... ##################################################################### the second effect, that of rainfall backscatter is even more pronounced as rain clutter rf return is inversely proportional to the fourth power of the wavelength (ref: "Antennas and Radiowave Propagation", Robert Collin) hence the 3 GHz s-band set would experience approx 81 times greater clutter return strength due to rain than the 1 GHz l-band set... ################################################################ the greater clutter return would mean it would have to expend more processing to try and extract valid target return signals from the background clutter (ie. decorrelate the clutter, etc)... note we are not including use of polarization here to mitigate rain backscatter effects (specifically circular polarization)...
milstar: Ka-band ADCs and DACs offer the potential to extend software-defined radio to software-defined microwave for satellite communication https://www.ednasia.com/ka-band-adcs-and-dacs-enhance-satellite-communication/ o support the move to Ka-band, Teledyne e2v started research in 2019 investigating the potential of a novel K-band (18 to 27 GHz) ADC, realised using a 24 GHz front-end, track and hold amplifier and a quad ADC interleaving the four digitiser cores. A prototype was developed and testing revealed that optimising INL calibration for higher frequencies, as opposed to baseband operation, as well as minimising the offset mismatch between individual ADCs, could maximise dynamic K-band performance (Figure 4). Fmax for 90 nm SiGe heterojunction bipolar transistors (HBTs) is currently 600 GHz. In 2020, a second prototype was developed combining two CMOS, interleaved, quad ADCs and a SiGe 30 GHz track and hold amplifier. Flip-chip die with lower parasitics at higher frequencies were mounted onto a low-dielectric constant organic substrate and placed in a compact 33×19 mm SiP, as shown in Figure 5. Improved performance was measured at K-band. Following the research carried out in 2019 and 2020, Teledyne e2v plans to release samples of the first Ka-band ADC for space applications in the second half on 2021. The SiP product will include a 40 GHz, front-end, track and hold amplifier to allow direct sampling of Ka-band carriers. First samples of the Ka-band ADC and DAC will become available this year with procurement and qualification options, as well as radiation-hardness data, to be released shortly after. To offer the space industry further integration and on-board processing benefits, SiPs will also be offered combining microwave ADCs and DACs with qualified FPGAs in a compact form factor (Figure 8). The first product will baseline Xilinx’s XQRKU060 device as illustrated below, with additional space-grade FPGAs planned as part of the overall roadmap.
milstar: Advanced wide band sampling solution for direct digitization of the K-band – extending the boundaries of RF possibility. https://edn.com/wp-content/uploads/Wide-band-sampling-solution-White-Paper-Update.pdf
milstar: Typically, a first pass of the spectrum segment is done at high bandwidth to pull in as much data as possible to obtain areas of interest to analyze, after which a higher-resolution, lower-bandwidth solution is leveraged to focus on specific targets. As warfighters see a far greater range of the spectrum, more lives are saved and mission success probability is increased because of faster, more accurate identification of threats and improved response options. https://militaryembedded.com/radar-ew/signal-processing/sige-based-warfare-processing-performance .Ka-band ADCs and DACs offer the potential to extend software-defined radio to software-defined microwave for satellite communication and EW 1.В России есть 0.25 SiGe можно реализовать https://link.springer.com/article/10.1007/s10470-009-9422-7 ENOB of 7.2-bits at an input frequency of 3.125 GHz and a sampling rate of 12.5 GS/s with a FOM of 12.9 pJ per conversion. Both DNL and INL are within 0.5 and 1 LSB, respectively. The converter occupies 10 mm2 and dissipates 14 W from a 3.3 V supply. ################# 2..китайская разработка ,0.18 - может помогут России с процессом ? https://www.jstage.jst.go.jp/article/elex/16/3/16_16.20181079/_pdf In this paper, a time-interleaved 10-GS/s 8-bit analog-to-digitalconverter (ADC) fabricated in 0.18 μm SiGe BiCMOS technology has beendemonstrated ######################## 3. SiGe-based ADCs/DACs double COTS Electronic Warfare processing performance https://militaryembedded.com/radar-ew/signal-processing/sige-based-warfare-processing-performance ######################### 4. Ka-band ADCs and DACs offer the potential to extend software-defined radio to software-defined microwave for satellite communication https://edn.com/wp-content/uploads/Wide-band-sampling-solution-White-Paper-Update.pdf https://www.ednasia.com/ka-band-adcs-and-dacs-enhance-satellite-communication/ o support the move to Ka-band, Teledyne e2v started research in 2019 investigating the potential of a novel K-band (18 to 27 GHz) ADC, realised using a 24 GHz front-end, track and hold amplifier and a quad ADC interleaving the four digitiser cores. A prototype was developed and testing revealed that optimising INL calibration for higher frequencies, as opposed to baseband operation, as well as minimising the offset mismatch between individual ADCs, could maximise dynamic K-band performance (Figure 4). Fmax for 90 nm SiGe heterojunction bipolar transistors (HBTs) is currently 600 GHz. In 2020, a second prototype was developed combining two CMOS, interleaved, quad ADCs and a SiGe 30 GHz track and hold amplifier. Flip-chip die with lower parasitics at higher frequencies were mounted onto a low-dielectric constant organic substrate and placed in a compact 33×19 mm SiP, as shown in Figure 5. Improved performance was measured at K-band. Following the research carried out in 2019 and 2020, Teledyne e2v plans to release samples of the first Ka-band ADC for space applications in the second half on 2021. The SiP product will include a 40 GHz, front-end, track and hold amplifier to allow direct sampling of Ka-band carriers. First samples of the Ka-band ADC and DAC will become available this year with procurement and qualification options, as well as radiation-hardness data, to be released shortly after. To offer the space industry further integration and on-board processing benefits, SiPs will also be offered combining microwave ADCs and DACs with qualified FPGAs in a compact form factor (Figure 8). The first product will baseline Xilinx’s XQRKU060 device as illustrated below, with additional space-grade FPGAs planned as part of the overall roadmap. https://semiconductors.teledyneimaging.com/en/products/data-converters/analog-to-digital/
milstar: Most advanced microwave capable ADC generating signal waveforms in multiple frequency bands up to KA https://www.youtube.com/watch?v=EIZmF3t9n7s
milstar: https://download.tek.com/document/Tek049%20Oscilloscope%20ASIC%20whitepaper%2055W-61320-0.pdf The new 12-bit ADC is the fastest in the world, running internally at 25 GS/s to give it a 25% higher sample rate per chan-nel than previous oscilloscopes in its class. The 12 bits allow for 4096 vertical digitizing levels, providing 16x more reso-lution than other oscilloscopes utilizing 8-bit ADCs. Each ADC channel is based on an interleaved Successive Approxi-mation Register (SAR) architecture, and each Tek049 chip includes four ADCs for a total throughput of 100 GS/s
milstar: RF sampling: Learning more about latency https://e2e.ti.com/blogs_/b/analogwire/posts/rf-sampling-learning-more-about-latency compare Teledyne e2v’s EV12AS350 is set to be the only 12-bit resolution ADC on the market that combines signal digitization at 5.4GSps, input bandwidth in excess of 4.8GHz and latency as low as 26 clock cycles with a noise of -150dBm/Hz. Unlike other ADCs on the market, it will be free of non-harmonic spurs, creating a pure signal for coders to manipulate in a range of demanding applications. https://semiconductors.teledyneimaging.com/en/products/data-converters/ev12as350b/
milstar: The TADF-4300 module supports sampling in the 2nd nyquist zone, to analyze signals as high as 8 GHz and provides sub-30-nanosecond latency for the A/D converter and sub 10 nanoseconds for the D/A converter https://www.militaryaerospace.com/trusted-computing/article/16715390/6u-vpx-card-set-for-ew-sigint-and-digital-radio-processing-introduced-by-curtisswright
milstar: Navy experts also will use the Curtiss-Wright SVME-183 computer boards for the Navy's AN/TPS-59(V)3 tactical missile defense radar, which can detect and track aircraft and missiles at ranges as far as 300 nautical miles. The value of the Navy contract to Curtiss-Wright has yet to be negotiated. The AN/TPS-59 from the Lockheed Martin Corp. Mission Systems and Training segment in Syracuse, N.Y., is a three-dimensional solid-state linear-phased array surveillance radar that operates in the D band (1215-1400 MHz), and has 54 transmitters that operate independently, and can also operate in the two-dimensional mode should its general-purpose computer fail. https://www.militaryaerospace.com/computers/article/16715347/navy-chooses-6u-vme-singleboard-computers-from-curtisswright-for-shipboard-radar
milstar: https://www.lockheedmartin.com/content/dam/lockheed-martin/rms/documents/ground-based-air-surveillance-radars/TPS-59%20Fact%20Sheet.pdf AN/TPS-59
milstar: We discuss a 12-b 18-GS/s analog-to-digital converter (ADC) implemented in 16-nm FinFET process. The ADC is composed of an integrated high-speed track-and-hold amplifier (THA) driving up to eight interleaved pipeline ADCs that employ open-loop inter-stage amplifiers. Up to 10 GS/s, https://ieeexplore.ieee.org/document/9210069
milstar: Analog device 14 bit 5 gsps 28nm process https://ieeexplore.ieee.org/document/7573537
milstar: https://web.wpi.edu/Pubs/E-project/Available/E-project-121012-102852/unrestricted/Evaluation_of_a_Microwave_Receiver.pdf he superheterodyne architecture has been the most popular choice for radio frequency(RF) receivers for the past 70 years, but the rise of high-speed sampling devices has caused experts to question the dominance of this architecture in receiver design. Ideally, the goal of all receiver designers is to connect the antenna directly to the digital signal processor (DSP), but our current level of technology cannot achieve this goal. The use of high-speed sampling devicesworks toward this goal: it shortens the analog portion of the RF front end of the receiver and moves the antenna closer to the DSP. The goal of this project was to build a new receiver architecture around a high-speed sampling device and compare it to the superheterodynearchitecture currently deployed by our sponsor.
milstar: An Adaptable 6.4 - 32 GS/s Track-and-Hold Amplifier with Track-Mode Masking for High Signal Power Applications in 55 nm SiGe-BiCMOS This paper presents a track-and-hold amplifier based on a switched emitter follower with demonstrated sampling rates from 6.4 GS/s to 32 GS/s and an analog bandwidth of up to 19 GHz in the hold-mode. Linearity measurements in the first Nyquist zone show 4.9 - 7.9 bits of accuracy for the highest sampling rate, more than 6 bits for up to 25.6 GS/s, more than 7 bits for up to 12.8 GS/s and a maximum of 8.9 bits at 6.4 GS/s, all calculated from the SNDR values. Most comparable circuits use only the THD value to calculate ENOBs, since achieving high SNR is difficult for low signal power circuits. The measurement results of the proposed track-and-hold amplifier were obtained at a high differential input voltage swing of 2.0 Vpp while they can reach even higher values at 1.0 Vpp. The 1-dB compression point is even higher, at 18.9 dBm. This makes the circuit suitable for high signal or noise power applications that demand high data rates and high linearity at the same time, including radio frequency instrumentation and receivers in radar and satellite communications. Designed as the front-end of a folding ADC, an additional benefit is the track-mode masking, recovering the common-mode level of the outputs during the input track-mode, which can be important when working with high input voltages. The third-order intercept point of 27.4 dBm at 25.6 GS/s and up to 34.7 dBm at 6.4 GS/s shows the unique combination of high signal power and high linearity in a sampling circuit above 10 GHz. This is made possible by the modern 55 nm SiGe-BiCMOS technology with high-performance HBTs. https://ieeexplore.ieee.org/document/8550911 This paper demonstrates a high-linearity track-and-hold circuit for sampling rates from 6.4 GS/s to 32 GS/s. It shows up to 19 GHz bandwidth and 8.8 bits of accuracy at a 2 Vpp differential input voltage swing. This is more than comparable high-frequency sampling circuits achieve with considerably lower input voltage range and leads consequently to the highest third-order intercept point of up to 34.7 dBm, even more than the best compared circuit achieves in InP technology. Especially CMOS sampling circuits have very restricted input swings and are not well suited for oscilloscopes and noisy environments. In particular, the implemented THA allows application in time-interleaved or single-core digitizing systems with a nominal resolution of up to 9 bits. While accuracy is higher than 7 bits until 12.4 GHz signal frequency at sampling rates up to 12.8 GS/s, the first two Nyquist zones or more can be used in this case. This can simplify system architecture significantly, since one low-pass filter is sufficient to suppress harmonic distortions of the input signal at every frequency from the second Nyquist zone on. Finally, the presented circuit can contribute to cover entire frequency bands in RF & microwave communications up to the Ka band.
milstar: https://www.analog.com/media/cn/technical-documentation/apm-pdf/adi-civilian-radar-solutions_en.pdf Visit analog.comRadar Application Introduction
milstar: One key element in the realization of a “true” digital radar intermediate-frequency (IF) receiver is the track-and-hold amplifier (THA). We propose that a THA plus a high-speed (1 to 1.5 GS/s), high dynamic range (8 to 10-bit) analog-to-digital converter (ADC) be employed to directly sample a 4 GHz IF signal present in our current-generation SAR systems. A simplified block diagram of the RF subsystem, showing the 4 GHz IF output, is shown in Figure 1. Sandia Lab https://core.ac.uk/download/pdf/192856533.pdf
milstar: THAs offer precision signal sampling over 18 GHz bandwidth, with 9-bit to 10-bit linearity from dc to beyond 10 GHz input frequencies, 1.05 mV noise, and <70 fs random aperture jitter. The device can be clocked to 4 GSPS with minimal dynamic range loss—such cases include the HMC661 and HMC1061. These THAs can be used to expand the bandwidth and/or high-frequency linearity of high-speed analog-to-digital conversion and signal acquisition systems. https://www.allaboutcircuits.com/industry-articles/extending-bandwidth-x-band-frequencies-a-track-and-hold-sampling-amplifier/
milstar: Process Wide Bandwidths in Aerospace/Defense Systems Low probability of intercept (LPI) and low probability of detection (LPD) are classes of radar systems with certain performance characteristics which make them nearly undetectable by modern intercept receivers. LPI features prevent the radar from tripping off alarm systems or passive radar-detection equipment. To provide resistance to jamming, radar systems can be architected by intelligently randomizing and spreading radar pulses over a wide frequency band so that a limited amount of signal energy will be present in any one band, using a technique known as direct-sequence-spread-spectrum (DSSS) modulation (Fig. 2). Frequency-hopping-spread-spectrum (FHSS) is another method of moving signal energy around the available bandwidth to make it more difficult to jam the signals. In these cases, more bandwidth is consumed than would normally be needed for the signal of interest. As a result, a wider receiver bandwidth is required in support of such anti-jamming approaches. 2. Direct-sequence-spread-spectrum (DSSS) systems require a wide receiver bandwidth and high dynamic range as the signal band of interest is combined with pseudorandom noise (PN) to spread communications signals into the noise floor. One of the most important factors for success in an LPI system is the use of as wide a signal transmission bandwidth as possible to disguise complex waveforms as noise. This conversely provides a higher-order challenge for intercept receiver systems that seek to detect and decipher these wideband signals. Therefore, while this creates improvements towards LPI and LPD functions, it also increases radar transceiver complexity by mandating a system that can capture the entire wide transmission bandwidth at once. The capability of an ADC to simultaneously digitize 500 MHz, 1 GHz, and larger portions of spectrum bandwidth in a single Nyquist band provides the means to tackle this system-level challenge. Moving these bands higher in frequency, beyond the first Nyquist band of an ADC, can be even more valuable. https://www.mwrf.com/technologies/mixed-signal-semiconductors/article/21846697/process-wide-bandwidths-in-aerospacedefense-systems
milstar: http://www.ecrin.com/datasheets/VADATECH/AMC526-Spec.pdf
milstar: How error-correction IP provides 20db improvements in high-speed ADC systems https://www.youtube.com/watch?v=mOYmMhxM15w
milstar: To explore this further, Figure 1 illustrates a high level overview of a typical current X-band radar system. Within this system, two analog mixing stages are typically utilized. The first stage mixes the pulsed radar return to a frequency of around 1 GHz and the second to an IF in the region of 100 MHz to 200 MHz to enable sampling of the signal using a 200 MSPS or lower ADC, to a resolution of 12 bits or higher. https://www.analog.com/en/technical-articles/the-demand-for-digital.html
milstar: As an example, take AD9680 and AD9695, which were designed using the 65 nm and 28 nm CMOS technology, respectively. At 1.25 GSPS and 1.3 GSPS, the AD9680 and AD9695 burn 3.7 W and 1.6 W, respectively. This shows that for the same architecture, give or take, the same circuit can burn about half the power on a 28 nm process as it did on a 65 nm process. The corollary to that is you can run the same circuit at twice the speed on 28 nm process, as you did at 65 nm while burning the same amount of power. The AD9208 illustrates this to a good extent. https://rfengineer.net/rfic/high-speed-adc-power-supply-domains/
milstar: re:параллельный прием, множество каналов в приемнике LRASM,,повсеместная РЛС 1.B-1B может нести во внутренних отсеках до 24 таких ракет массой чуть более тонны каждая. Такого количества целей технически вполне достаточно для того, чтобы обеспечить корабельной ПВО, и даже не китайской, "перегрузку по входу". Роберт Уорк, в прошлом заместитель министра обороны США. https://vpk.name/news/292117_sovetskii_metod_zachem_aviacii_vms_ssha_nuzhny_dalnie_raketonoscy.html ################################################################## 2. a. главной особенностью ЗРС «Бук-М2», ее изюминкой, являются значительно расширенные возможности по борьбе с современными КР на предельно малых высотах. Так, при полете КР на высоте 15 м дальность ее поражения составляет до 30–35 км, Это достигается за счет введения в состав ЗРС радиолокатора подсвета и наведения (РПН)-9C36M , антенные системы и приемно-передающие устройства которого размещены на мобильном телескопическом подъемно-поворотном устройстве, поднимающем их на высоту более 22 м в течение 2 мин. Александр Григорьевич Лузан, доктор технических наук, лауреат Государственной премии, генерал-лейтенант в отставке, https://www.vesvks.ru/vks/article/tomagavki-byut-po-sirii-poleznye-uroki-16280 2.b http://bastion-karpenko.ru/viking-buk-m3/ антенна бук м3 9C36M Ku -38 db ,ширина луча 1 * 2 градуса , предположительно 7.6-8 ghz , 2500 -3000 элементов при полном заполнении из расчета h/2 ... возможно реализовать среднюю мощность 10 квт при PRF =1000 ,интеграции 20 импульсов реалистичнo получить дальность обнаружения 140 километров для RCS = 1 квадратный метр,35 километров для RCS = 0.004 квадратный метра ########################## 3.повсеместный радар,параллельный прием множеством приемников в АФАР с полностью цифровым формированием лучей Dr. Eli Brookner, Raytheon http://radarconf16.org/tutorial-c3.pdf Digital Beam Forming (DBF): Israel, Thales and Australia AESAs under development have an A/D for every element channel https://apps.dtic.mil/dtic/tr/fulltext/u2/a403877.pdf Systems Aspects of Digital Beam Forming Ubiquitous Radar MERRILL SKOLNIK https://www.raytheon.com/sites/default/files/capabilities/rtnwcm/groups/public/documents/image/amdr-infographic-pdf.pdf 69 RMA ( каждый 61*61*61 сантиметр )provide SPY-1 +25 db capability can see a target of half the size at almost four times the distance 37 RMA (configuration for DDG 51 Flight 3) can see a target half the size at twice the distance of radar on today's navy destroyers Dual Axis multibeam scanning Thales http://tangentlink.com/wp-content/uploads/2014/12/4.-AESA-radars-using-Dual-axis-Multibeam-Scanning.pdf 4. один из возможных сценариев противник как в пункте 1 желает создать перегрузку po входу 96 ракет LRASM на высоте 2-5 метра в секторе 90 градусов равноудаленных от рлс на высотe 22 метра как в пункте 2 повсеместная РЛС 2500 -3000 элементов , средняя мощность передатчика = 10 квт ширина луча 2 градуса пo вертикали,1. градуса пo горизонтали передающие блоки повсеместной РЛС формируют сектор из 90 лучей 90*1 градус *2 градусa энергетический потенциал каждого луча падает в 90 раз,это компенсируется увеличением времени интеграции в 90 раз в каждом луче сектора copy from 2b при PRF =1000 ,интеграции 20 импульсов реалистичнo получить дальность обнаружения 140 километров для RCS = 1 квадратный метр,35 километров для RCS = 0.004 квадратный метра ----------------------------- 0.02 секунды *90 =1.8 сек время интеграции 1800 импульсов, вполне допустимо так как скорость LRASM =300 metr sek ,.для сравнения РЛС 300в4 ПО 9С19М1 «Имбирь-М» концентрированная для перехвата Першинг- 2 ( скорость более 3000 метров в секунду) темп обновления информации – 1 с https://www.vesvks.ru/vks/article/zenitnaya-raketnaya-sistema-s300v4--nadezhnyy-stra-16279 более детальные расчеты в тексте page 7 short -range surveillance https://apps.dtic.mil/dtic/tr/fulltext/u2/a403877.pdf Systems Aspects of Digital Beam Forming Ubiquitous Radar MERRILL SKOLNIK A radar that can detect 1 sqare metr target at 140 nmi with a 4-s revisit time can detect the same size target at 100 nmi (185.2 km) with a 1-s revisit time.(Coherent integration is assumed.) Then there is enough echo signal energy at 10nmi (18.52 km) to detect a 0.0001 m2 target with a 1-s revisit time,assuming that doppler signal processing is used that provides an adequate signal-to-clutter ratio. If the radar requires a 0.1s revisit 10 nmi =18.52 km time to guide a defensive missile to an intercept, the minimum detectable radar cross section is then 0.001 sqare metr .If it were really important to place a 0.0001 m2 cross section target in track with a 0.1s revisit time that could be done at a range of about 5.6 nmi.(10km) ##################################### 5, Российские компоненты СБИС 16-разрядного АЦП с частотой дискретизации 200 МГц https://mri-progress.ru/products/bis-i-sbis/spetsialnye-sbis/sbis-16-razryadnogo-atsp/ Микросхема интегральная 1879ВМ8Я представляет собой универсальную платформу ориентированную на решение задач обработки больших потоков данных в реальном масштабе времени (цифровая обработка сигналов, обработка изображений, навигация, связь, https://www.module.ru/products/1/26-18798
milstar: 2 -Доктрина «На войне, — оборонительный образ действий никогда не должен иметь целью только оборону; он всегда должен иметь единственной целью использование собственных средств с наибольшим коэфициентом полезного действия... Наоборот, воздушная оборона имеет целью только защиту. Она ничуть не повышает коэфициента использования воздушного оружия, а даже уменьшает его до минимума. Таким образом, она представляет собой военно-техническую ошибку» ...Наконец, есть образ, действий, повидимому, соединяющий в себе все трудности: это — оборона в воздухе. «Воздушному оружию нет надобности яростно набрасываться на небольшие объекты, так как перед ним открывается бесчисленное количество крупных и важных объектов... Воздушное оружие будет испытывать затруднения лишь в выборе. Самыми первыми объектами воздушной армии должны быть неподвижные и постоянные объекты, обслуживающие воздушные силы противника: самолетостроительные заводы, крупные склады имущества и т. п. Дуэ (сентябрь 1928 г.). ....ввести в состав дивизиона комплексы Циркон,X-95 --------------------------------------------------------- при потере связи командиру дивизиона предоставлена атаковать неподвижные цели военно-воздушных сил противника аэродромы ,пункты командования ВВС,РЛС противоракетной обороны, базы ВМФ и ВВС в том числе термоядерными боевыми блоками ----------------------- для сравнения доктрина 80 годов предполагала использование ядерного оружия как одного из средств радиоэлектронной борьбы Другой подход (с начала 60-х и до конца 80-х гг.) состоял в том, что составной частью РЭБ считалось поражение РЭС противника любыми средствами, включая даже ядерное поражение, Михаил Дмитриевич Любин - полковник в отставке, бывший старший преподаватель кафедры РЭБ Военной академии Генерального штаба. ----------------- на рисунке в статье Александр Лузан, доктор технических наук, лауреат Государственной премии РФ, генерал-лейтенант прикрытие Искандеров https://vpk-news.ru/articles/36010
полная версия страницы